Oscilloscopes,

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Oscilloscopes

This Page Intentionally Left Blank

Oscilloscopes H o w to use them, h o w they work Fifth Edition

Ian H i c k m a n BSc (Hons), CEng, MIEE, MIEEE

AMSTERDAM ELSEVIER

9BOSTON

PARIS ~ SAN DIEGO

~ HEIDELBERG

~ SAN FRANCISCO

~ LONDON

Newnes

~ NEW YORK

~ SINGAPORE

B~WORTI-I

is a n i m p r i n t o f E l s e v i e r

~ SYDNEY

9OXFORD ~ TOKYO

Newnes An imprint of Elsevier Linacre House, Jordan Hill, Oxford OX2 8DP 30 Corporate Drive, Burlington, MA 01803 First published 1981 Reprinted 1984 Second edition 1986 Revised reprint 1987 Reprinted 1989 Third edition 1990 Reprinted 1992, 1994 Fourth edition 1995 Reprinted 1997, 1998, 1999 Fifth edition 2001 Reprinted 2004, 2005 Copyright 9 1986, 1990, 1991, 1995,2001. Elsevier Ltd. All rights reserved No part of this publication may be reproduced in any material form (including photocopying or storing in any medium by electronic means and whether or not transiently or incidentally to some other use of this publication) without the written permission of the copyright holder except in accordance with the provisions of the Copyright, Designs and Patents Act 1988 or under the terms of a licence issued by the Copyright Licensing Agency Ltd, 90 Tottenham Court Road, London, England W 1T 4LP. Applications for the copyright holder's written permission to reproduce any part of this publication should be addressed to the publisher Permissions may be sought directly from Elsevier's Science & Technology Rights Department in Oxford, UK: phone: (+44) 1865 843830, fax: (+44) 1865 853333, e-mail: [email protected]. You may also complete your request on-line via the Elsevier homepage (http://www.elsevier.com), by selecting 'Customer Support' and then 'Obtaining Permissions'

British Library Cataloguing in Publication Data A catalogue record for this book is available from the British Library Library of Congress Cataloguing in Publication Data A catalogue record for this book is available from the Library of Congress ISBN 0 7506 4757 4 For information on all Newnes publications visit our website at www.newnespress.com

Composition by Genesis Typesetting, Laser Quay, Rochester, Kent Printed and bound in Great Britain by Biddies Ltd, King's Lynn, Norfolk

Contents Preface

vii

Preface to fifth edition

ix

1. Introduction

1

2. The basic oscilloscope

8

3. Advanced real-time oscilloscopes

18

4. Accessories

33

5. Using oscilloscopes

52

6. Sampling oscilloscopes

88

7. Digital storage oscilloscopes

115

8. Oscilloscopes for special p u r p o s e s

149

9. H o w oscilloscopes w o r k (1): the c.r.t.

176

10. H o w oscilloscopes w o r k (2): circuitry

188

11. H o w oscilloscopes w o r k (3): storage c.r.t.s

213

A p p e n d i x 1 Cathode ray tube p h o s p h o r data

250

A p p e n d i x 2 Oscilloscope manufacturers and agents

253

Index

257


Preface W h o is this book m e a n t for? It is for a n y o n e w h o is interested in oscilloscopes, h o w to use t h e m and h o w they work, and for a n y o n e w h o might be if he or she k n e w a little more about them. It is easy to say w h a t the book is not: it is not a textbook of any sort, and particularly not a textbook on h o w to design oscilloscopes. Nevertheless, besides describing a great variety of oscilloscopes, their particular advantages and h o w to use them, the book explains briefly h o w these instruments work, on the basis that the best drivers have at least some idea of w h a t goes on u n d e r the bonnet. This takes us into electron physics and circuit t h e o r y - but not too far. Formulae and results are simply stated, not derived or proved, and those with only the haziest knowledge of mathematics will find n o t h i n g to alarm t h e m in this book. Consequently, readers in their earliest teens will be able to learn a lot from it; Chapter 1 is written especially for a n y o n e with no prior knowledge of the subject. Sixth-formers and students on ONC and HNC courses should all find the book useful. Even m a n y degree students will find it of considerable help (though they m a y choose to skip Chapter 1!); electronic engineering undergraduates have plenty of o p p o r t u n i t y to learn about oscilloscopes, but m a n y graduates come into electronic engineering from a physics degree course, and will welcome a practical introduction to oscilloscope techniques. Technicians and technician engineers in the electronics field will of course be used to oscilloscopes, but the following chapters should enlarge their understanding and enable t h e m to use the facilities of an oscilloscope to the full. Finally, I hope that those whose interest in electronics is as a hobby, including m a n y a m a t e u r radio hams and radio-controlled-model enthusiasts, will find the book valuable, especially if they are considering buying or even constructing their o w n oscilloscopes.


Preface to fifth e d i t i o n Keeping this book up to date is r a t h e r like painting Edinburgh's f a m o u s bridge over the Firth of Forth - no sooner do t h e y get to the e n d t h a n it's time to start all over again at the beginning. In the same way, no sooner does a n e w edition of this book come out t h a n one or other of the oscilloscopes illustrated or featured will go out of production, usually to be replaced by a later, i m p r o v e d model. A n d as for A p p e n d i x 2, one can m o r e or less g u a r a n t e e that by the time a n e w edition is in the offing, at least 50 per cent of the m a n u f a c t u r e r s or their agents will h a v e c h a n g e d their address or telephone number. As ever, the p e r f o r m a n c e a n d value for m o n e y offered by the c u r r e n t models h a v e a d v a n c e d considerably since the a p p e a r a n c e of the last (fourth) edition. This is a continuing source of mild surprise a n d quiet satisfaction for a n y o n e w h o has b e e n interested in the oscilloscope scene for a n y length of time - w h i c h in m y case a m o u n t s to nigh on fifty years. M y first scope, h o m e built for cheapness of course, was a h o m e b r e w conversion of an ex-RAF Indicator Unit Type 182A, w h i c h incorporated a VCR517C cathode ray tube. The unit was available on the p o s t - w a r military e q u i p m e n t surplus m a r k e t for a few pounds, a lot of m o n e y in those days - especially for a lad still at school. Even so, it was considerably c h e a p e r t h a n units containing the m o r e p o p u l a r VCR97 cathode ray tube, w i t h its shortpersistence green phosphor. So, for reasons of financial stringency, m y first oscilloscope h a d a long persistence cathode ray tube w i t h a blue 'flash' a n d yellow 'afterglow'. In its original role as a radar display, a glass filter tinted deep yellow in front of the screen suppressed the flash, but I r e m o v e d this, m a k i n g the tube r a t h e r less inappropriate for oscilloscope duty. Nevertheless, the afterglow was always a nuisance except for single shot applications or during e x t e n d e d observation of a stable triggered w a v e f o r m - u n f o r t u nately I n e v e r t h o u g h t of putting a deep blue filter in front of the screen. (A s u b s e q u e n t conversion to TV use was e v e n less

x Preface to fifth edition

satisfactory. Apart from blurred lips. the newsreader was not too bad but a football match was a disaster. The blue ball with its long curved yellow tail looked like a comet, and when thc camera panned from onc end of thc ground to the ot.her, confusion reigned supreme.) A scopc with a long-persist.erice screen is still very ~ i ~ c fin ~il certain applications, where it can form ;1 very much cheaper oplion than a variable-persistence storage oscilloscope or a DSO (digital storage oscilloscope) of similar bandwidth. Oscilloscopcs offcring the option of a cathode ray tube with a long-pcrsistcnce screen in place of a standard one are by now unobtainable, but many longpersistence scopes are still in regular use. Thus in the world of the oscilloscope, the old and the ne w both continue to be useful, each in its appropriate sphere. Another example of this is the ‘second user market’, an area of steadily growing importance. As Government Departments and Agencies and large firms re-equip themselves with the latest and best in oscilloscopes, large quantities of used but perfectly serviceable equipment are released. Most of this finds its way onto he second user market, where dealcI-s specializing i n this trade offer i t f o r resale. The riiore reputable dealers will have had the c q u i p ~ i c novcrha l u l c ~ and l rccalibrated to good-as-new condition, d n d i t thcn represents cxccllcnt vnluc for t h c srnallrr company, the indcpendcnt consullaill a n d w e n thc kccn clcctronics cnthusias~., I r i !his way, a n cxccllcnt oscilloscope, sprct i - i i n i analyser or other instrumcnt (adtnillcdly of a rnodcl often no 1ongc.t. i t 1 production) can be obtained l o r somewhere betwccii a tc.n~hand a fifth of the price of its current new equivalun1. The m a j o r manufacturers continue t o support such instrumcnts f o r some eight to ten years after the model was discontinued. So a bargain scope can be repaired a n d maintained as necessary, giving many years of faithful servicc., especially if returned to the maker for a complete overhaul j list before the period of support expires. This f i l t h edition of the hook, which was lirst published in 1981 and has never been o u t of print since, ha\ been extensively revised. Chapter 11, describing how storage cathode ray tubes work, has been retained. It was added at the third edition when ’analogue’ storage scopes (i.e. those using direct-view storage c.r.t.s) were

Preface to fifth e d i t i o n

xi

available from a n u m b e r of manufacturers. This is no longer the case, so perhaps the logical m o v e might seem to be the omission of the chapter in its entirety. But it has been retained, for a n u m b e r of reasons. Firstly, the description of the operation of storage c.r.t.s illustrates some interesting aspects of electron optics, a branch of physics on w h i c h all c.r.t.s depend for their operation. Secondly, with the m a r c h of time, sources of information on the m o d u s operandi of storage cathode ray tubes will become rarer and rarer. Thirdly and m o r e importantly, m a n y analogue storage scopes are still in use, a n d some guidance on their advantages, limitations and quirks m a y not come amiss. And while oscilloscopes using a storage cathode ray tube no longer seem to be available (except on the second user market), one of the major oscilloscope m a n u f a c t u r e r s still produces analogue storage oscilloscopes, using a 'scan converter tube'. The principle of operation of these is also t o u c h e d on in Chapter 11. The chapter has therefore been retained, but with the substantial pruning carried out at the previous (fourth) edition, while still covering all the fundamentals of the subject. The book n o w includes photographs of later models of some of the instruments which were illustrated in the fourth edition, plus details and photographs of instruments from various m a n u facturers whose product lines were not previously represented in these pages, whilst illustrations of models no longer available have, with but one or two exceptions, been removed. The author gratefully acknowledges the m a n y m a n u f a c t u r e r s and their agents w h o have assisted by providing information on, and pictures of, their products. F r o m these, a selection of photographs has been included illustrating real-time oscilloscopes, both storage and non-storage, sampling and digital storage oscilloscopes and their accessories. In each case, the caption at least gives brief details of the performance of the instrument, whilst in several cases it has been possible to give a more extensive account of its performance in the text. My special thanks are due to Tektronix UK Ltd for providing material u p o n which I have d r a w n freely in Chapters 6 and 11 and elsewhere, and for other valued assistance. I.H.

October 2000

~

v

An advanced orcillowrpc of th e 1940s. Thc Cossor niodcl 1 0 3 5 M k l 1A was a true ~iii of 7 MHr ( Y I amplifier), dual beam oscilloscope with a ~ ~ i a x i r i i ~bandwidth 100 kHz j Y 2 anqilifirrj and a fasrcst sweep rate of 1 5 p per scan, with repetitive, triggered and single-stroke operation (courtesy Coscor Electronics Lid)

1

Introduction

The cathode ray oscilloscope is an instrument designed to display the voltage variations, periodic or otherwise, that are met with in electronic circuits and elsewhere. The word is an etymological hybrid. The first part derives from the Latin, to swing backwards and forwards; this in turn is from oscillum, a little mask of Bacchus h u n g from the trees, especially in vineyards, and thus easily m o v e d by the wind. The second part comes from the Classical Greek skopein, to observe, aim at, examine, from which developed the Latin endingscopium, which has been used to form names for instruments that enable the eye or ear to make observations. For some reason the subject of the design and use of oscilloscopes is generally not called oscilloscopy but oscillography, from oscilloand graphein, to write. There are other types of oscilloscope besides those using cathode ray tubes. For example, pen recorders, ultra-violet chart recorders and XY plotters are all oscilloscopes or oscillographs of a sort, as indeed is 'Fletcher's Trolley' of school physics fame. However, this book is concerned mainly with cathode ray oscilloscopes, together with the increasing n u m b e r of similar instruments using LCD (liquid crystal display) technology. R e p r e s e n t i n g a v a r y i n g voltage The basic principle of oscillography is the representation, by graphical means, of a voltage that is varying. The voltage is plotted or traced out in two-dimensional Cartesian coordinates, n a m e d after Descartes, the famous French s e v e n t e e n t h - c e n t u r y philosopher and mathematician. Figure 1.1 shows the general scheme for the representation of any two related variables. Both positive and negative values of each variable can be represented. The vertical axis is called the Y axis, and the horizontal the X axis. The point w h e r e the axes cross, where both X = 0 and Y = 0, is called the 'origin'.

9

9

9

~-,.

Oscilloscopes

4,

2

2

1

X

3

-1

-2 ~.

I

0

,_..,. ,._,

-1

,...,

-2

,-.] ,...~ :::~-'

, -3

'-"

-

.

,.m-4~

Figure 1.1 Cartesian o r graphical cnordinarcs. The horizontal and vertical axes may he two different scales, even diilcrrnt units, for graphical purposes

:....:j

" ~ ~

~.~

_~. ~.. ~

~

~

~,~

,-.

,-.,

~

~
60 dB CMRR at 60 Hz) can be floated up to 250 V off ground. Each channel is sampled a 200 ks/s, providing 20 kHz bandwidth. DSP-based filtering with a choice of lowpass, high-pass, band-pass or notch can be selected to combat noise problems (reproduced by courtesy of Astro-Med, Inc.)

isolation amplifier. Both current probes and isolation amplifiers are featured in later chapters.

Mainframe plus plug-in oscilloscopes M a i n f r a m e and plug-in oscilloscopes are designed for b e n c h operation rather t h a n portable use. The w e l l - k n o w n and longestablished Tektronix 7000 series m a i n f r a m e plus plug-in oscilloscope systems are no longer m a n u f a c t u r e d . But m a n y t h o u s a n d s are still in use t h r o u g h o u t the world and the m a n u f a c t u r e r supports each model in the range for eight years following the date w h e n it was discontinued. Consequently m a n y will be supported until after the year 2000, w h i c h explains the price that they still c o m m a n d on the second user e q u i p m e n t market. Figure 8.19 shows an example of a m a i n f r a m e oscilloscope. The advantage of the m a i n f r a m e plus plug-in format is economy, since if a different facility is n e e d e d it can be had for the cost of a plug-in, w h e r e a s otherwise a complete n e w oscilloscope w o u l d be required. On the other hand, only one person at a time can use the mainframe, so usually at a n y one time capital is tied

32 Oscilloscopes up in various plug-ins sitting in a cupboard. Most large electronics laboratories therefore sought to strike a balance, with some mainframe oscilloscopes plus a variety of plug-ins for versatility, and some stand-alone 'portable' scopes for economy. However, the trend recently is for stand-alone/portable oscilloscopes to become the norm, although a few manufacturers still offer instruments in the mainframe/plug-in format.

4

Accessories We have e x a m i n e d a variety of oscilloscopes in the previous chapters, b o t h simple and advanced. All are capable of examining waveforms as they stand: simply connect the circuit whose w a v e f o r m you wish to e x a m i n e to the Y input and the w a v e f o r m will appear on the screen (assuming the controls are suitably set). Actually, it is not quite that simple. Although the Y input of an oscilloscope has a very high input impedance, in m a n y cases its effect u p o n the circuit to which it is connected is not entirely negligible. The standard Y input resistance is 1 M ~ and the input capacitance is usually in the range 1 5 - 4 0 pF depending u p o n the particular m a k e and model. With such a high input impedance, h u m pick-up on the input lead w o u l d often be a p r o b l e m w h e n examining small signals in high i m p e d a n c e circuits unless a screened lead were used. However, one m e t r e of screened lead could easily add a n o t h e r 5 0 - 1 0 0 p F to the oscilloscope's input capacitance; on the other hand, trying to connect the circuit u n d e r test directly to the input connector of the scope with negligible lead lengths is always tedious and often impossible. The usual solution to this problem is a passive divider probe, and this is the first accessory at w h i c h we shall look.

Passive divider probes Experience shows that to connect an oscilloscope to a circuit u n d e r test, a lead about 1.5 metres in length is usually convenient, screened to avoid h u m pick-up w h e n working on h i g h - i m p e d a n c e circuits. Even a low-capacitance cable has a capacitance of about 60 pF/ metre, so a m e t r e of cable plus the input capacitance of the scope would result in about 100 pF of input capacitance. The purpose of a 10:1 passive divider probe is to reduce this effective input capacitance to a r o u n d 10 pF. This is a useful reduction, bearing in m i n d that at even a modest frequency like 10 MHz, the reactance of 100 pF is as low as 1 6 0 ~ .

34

Oscilloscopes

Figure 4.1(a) and (b) show the circuit diagram of the traditional type of scope probe, where Co represents the oscilloscope's input capacitance, its input resistance being the standard value of 1 M~. The capacitance of the screened lead plus the input capacitance of the scope form one section of a capacitive r ICT=

cc+Co ] g

I

I I '

I

l

I I1

probe tip

.•/'jf__

9M _~

/17-

_ _~u~ coax

ial

plug

lead capacitance : C C

earth connect Ion ~ (a)

CT

probe I scope

s

t y p i c a l equivalent ~nput c,rcu~t

}

A

Z%~l I

I I

v

cable c a p a c i t a n c e

Ro 1M

T

30p

I

(b) r

I I

1 cT

I

I I I

IJ~

RA, J~ I

I L__

9M

--~E-

l {c) Figure 4.1 (a) Circuit diagram of traditional 10"1 divider probe. (b) Equivalent circuit of probe connected to oscilloscope. (c) Modified probe circuit with trimmer capacitor at scope end (courtesy Practical Wireless)

Accessories

35

potential divider. The trimmer C T forms the other, and it can be set so that the attenuation of this capacitive divider is 10:1 in volts, which is the same attenuation as provided by RA (9 M{~) and the 1 M{~ input resistance of the scope. W h e n this condition is fulfilled, the attenuation is independent of f r e q u e n c y - Figure 4.2(a). Defining the cable plus scope input capacitance as CE, i.e. CE --- (Cc + Co), CT should have a reactance of nine times that of CE, i.e. CT = CE/9. If CT is tOO small, high-frequency components (e.g. the edges of a squarewave) will be attenuated by more than 10:1, resulting in the waveform of Figure 4.2 (b). Conversely, if CT is tOO large, the result is as in Figure 4.2(c). The input capacitance of the scope Co is invariably arranged to be constant for all settings of the Y input attenuator. This means that CT can be adjusted by applying a squarewave to the scope via the probe using any convenient Y sensitivity, and the setting will then hold for any other sensitivity setting. M a n y scopes provide a squarewave output on the front panel specifically for setting up passive divider probes. Such probes most commonly provide a division ratio of 10:1, but other values are sometimes found, e.g. the Tektronix P6009 100:1 probe operating to 120MHz with a m a x i m u m input capability of 1.5kV, and the P6015A 75MHz 40 kV probes. Some 10:1 probes have provision for shorting RA and CT to provide an alternative 1:1 ratio. W h e n using such a probe in the 1:1 mode, the capacitive loading on the circuit under

(a)

l ....

1 CT =CE]9 CE =Cr +CA+CO

(b)

cT

cE/9

(c)

CT > CE/9

Figure 4.2 Displayed waveforms with probe set up (a) correctly, (b) undercompensated, (c) overcompensated

36

Oscilloscopes

test is of coiirse ten limes as great as in the 10:l modc, and its use is t herefore confined mainly t o lowcr frcquencies. Thc circuit of Figure 4.1 ( a ) provides the lowest capacitivc circuit loading for a 1O:l divider probe, but has the disadvaniage that 90 per cenl oi the input vvltage (which could be very large) appcars across the variable capacitor CT. Some probes therefore use the circuit of Figure 4.1 (c ): CT is now a fixed capacitor and a variable shunt capacitor C, is fitted, which can be set to a higher or lower capacitance to compensate for scopes with a lower or higher input capacitance respectively. Now, only 10 per cent of the input voltage appears across the trimmer, which can also be conveniently located a t the scope end of the probe lead, permitting a smaller, neater design of probe head. Even if a 10:l passive divider probe (often called a x10 probe) is incorrectly set up, the rounding or pip on the edges of a very low-frequency squarewave, e.g. 50 Hz, will not be very obvious, because with the necessary slow timebase speed the squarewave will appear t o settle very rapidly t o the positive and negative Icvcls. Conversely, will1 a high-frequency squarewavc, say 1 MHz, thc division r a l i o will br determined solcly by the ratio C,/(7,. Wavdorms as i n Figure 4.2 will he seen a l Irr.qurrlcies or around 1 kHz. At very high frequencies, where the length of the probe lead is an appreciablc fraction of a wavelength, reflections occur, since the cablc is no1 rerminated in its characteristic impedance. For this reason, oscilloscope probes often incorporate a resistor of a few tens of ohms in series with the inner conductor of the cable a t o n e o r both cnds, or use a special cable with an inncr made of resistance wire. Such measures are necessary i n probes that are used with scopes having a bandwidth of 100 MHz or more. Special x10 divider probes are available for use in pairs with an oscilloscope with a Y1-Y.2 facility (Channel 1 plus Channel 2, with Channel 2 invcrled). By effectively making boih R, and CT adjustahle (see Figiirt. 4.1 :), thc gain of the scopc~'stwo Y channcls can tic cqualircd aT both high and low frequencies. For example, the Tektronix ditfercntial probe p i i - P6135A witfi its 1 5 0 M H z bandwidlh can ~irovidc2 0 0 0 0 : 1 CMRR (common mode re,jection ratio) from t1.c. t o I k l l z , derating l o 100:l a t 20MHz.

Accessories

37

Whilst a • passive divider probe greatly reduces loading on the circuit under test compared with a similar length of screened cable, its effect at high frequencies is by no means negligible. Figure 4.3 shows the typical variation of input impedance versus frequency w h e n using a xl 0 passive divider probe. Another point to watch out for w h e n using such a probe is the effect of the inductance of its ground lead. This is typically 150 nH (for a 15 cm lead terminated in an 'alligator clip'), and forms a resonant circuit with the input capacitance of the probe. On fast edges, this will result in ringing in the region of 150 MHz, so for high-frequency applications it is essential to discard the ground lead and to earth the grounded nose-ring of the probe to circuit earth by the shortest possible route. Not only the use of passive divider probes, but also the theory of their operation has been covered in this chapter (rather than in Chapter 10) because they are by far the c o m m o n e s t - and to that extent the m o s t i m p o r t a n t - oscilloscope accessory. Many a technician (and chartered engineer too) has wasted time wondering w h y the amplitude of a 10 MHz clock waveform, for example, was out of specification, only to realize eventually that t h e x l 0 probe being used was not correctly set up for use with that particular oscilloscope! 108

0-

-25

uJ 111 ~c 0 111 0 .5

V",

106

-

A

--,\,

!

AGNITUDE (OHMS)

,=

f

o9 -i-

-50

o

-

c_ N

,=

.

-75

-100

104 PHASE (DEGREES)

\

102

-

-

I

102

,,,,._._j' 104

106

-108

FREQUENCY

Figure 4.3 Variation of impedance at the tip of a typical x l 0 passive divider probe (courtesy Tektronix UK Ltd)

38 Oscilloscopes Active probes The reduced capacitive circuit loading provided by the passive divider probe is dearly bought, the price being a reduction in the sensitivity of the oscilloscope, usually by a factor of 10. An active probe can provide a 1:1 ratio, or even in some cases voltage gain, while still presenting a very low capacitive load to the circuit u n d e r test. This is achieved by m o u n t i n g a small unity gain buffer amplifier having a high input impedance and a low output impedance actually in the probe head. The probe has two leads, a coaxial cable to the Y input socket and a power supply lead which connects to an accessory p o w e r socket on the oscilloscope, or to a separate, special, free-standing probe power-supply unit. With the simple a r r a n g e m e n t described, the m a x i m u m signal that can usefully be applied to the probe is obviously limited by the input voltage swing that the probe head amplifier can handle. This can usually be increased by the use of 10:1 or 100:1 divider caps, clipped onto the probe's input. These not only increase the input voltage the probe can handle, but m a y also reduce the input capacitance even further. The extensive Tektronix range of active probes includes types with bandwidths up to 4.0 GHz with an input capacitance of 0.4 pF. The P6201 offers attenuations of 1:1, 10:1 and 100:1 all at 900MHz bandwidth and an input capacitance of 1.5 pF (3 pF at 1:1). The circuit of a typical active FET probe appears in Chapter 10. C u r r e n t probes The probes described so far, both active and passive, are designed for the m e a s u r e m e n t of w~ltage waveforms. However, probes are also available which measure current waveforms, very useful, for example, if one is developing a switch-mode p o w e r supply. There are passive current probes, but these usually have low sensitivity and a limited frequency response that does not extend d o w n to d.c., though they can be useful w h e r e these limitations are not important. Current probes usually have a slotted head, the slot being closed by a sliding member, after slipping in the wire carrying the current to be measured. There is thus no need to break the circuit

Accessories 39 in order to thread the wire t h r o u g h the probe. Current probes produce an output voltage identical to the w a v e f o r m of the current flowing in the wire. Some current probes w o r k d o w n to d.c., others are a.c. only. A typical, passive, a.c.-only probe can be plugged via its special passive t e r m i n a t i o n directly into an oscilloscope, t h o u g h in this m o d e the low-frequency cut-off point, depending on the particular probe, m a y be a n y w h e r e in the range from u n d e r 100 Hz to l kHz or more. For instance, the Tektronix P6021 has a b a n d w i d t h of 120 H z - 6 0 M H z with a 5.8 ns risetime and offers sensitivities of 2 0 m A / d i v and 1 0 0 m A / d i v (with the scope sensitivity set to 10mV/div). However, special amplifiers are available to interface an a.c.-only current probe to an oscilloscope; these not only increase the sensitivity of the probe, but extend its low-frequency cut-off point d o w n w a r d s by a factor of about 10. Thus the P6021 plus type 134 amplifier combination has a frequency response of 12 H z - 3 8 MHz, with the sensitivity increased to 1 mA/div. The amplifier works by having a negative input resistance, which largely cancels out the resistance of the probe's sensing winding. By reducing the sensing-circuit resistance to near zero, a lower induced voltage suffices to produce the output, keeping the required magnetizing current to a negligible fraction of the current being measured. Current probes with a frequency response d o w n to d.c. are usually active types t h o u g h most of the electronics is contained within an interface box to w h i c h the probe connects, and w h i c h has an o u t p u t which can be applied to the Y input socket of an oscilloscope. As well as the usual split core as in an a.c.-only probe, there is a Hall e l e m e n t for the d.c. and l o w - f r e q u e n c y response, as indicated in Figure 4.4(a). An example is the AM503S current probe system, consisting of the A6302 probe which, in conjunction with the m a t c h i n g AM503A current probe amplifier, provides a b a n d w i d t h of d.c. - 5 0 M H z and m e a s u r e s currents up to 20 A continuous, 50 A peak. There is an i m p o r t a n t point to bear in m i n d w h e n using current probes. W h e n using ordinary voltage transformers, the voltsecond product applied to the p r i m a r y m u s t be limited, to p r e v e n t core saturation. Thus a transformer designed for 440 Hz use can

40

Oscilloscopes

Ofl~

O

50t3

AMP

HALL DEVICE BIAS AMPLITUDE

DC

AMPLITUDE

100 kHz

50 MHz

f

BANDWIDTH CURVES

AMPLITUDE

|

(a)

100 kHz

50 MHz

1 A DC PLUS SIGNAL

100 mA

llll

AMPERE-TURNS

10 TURNS

(b) Figure 4.4 (a) Curren! transformer and Hall-effect device combined to provide a wide b a n d w i d t h extending d o w n to d.c. (b) Current bucking used to prevent core saturation is effective, but m a y affect h.f. performance (courtesy Tektronix UK Ltd)

Accessories

41

only support o n e - n i n t h of its rated primary voltage if used on 50 Hz mains. For current transformers, including current probes, there is a corresponding Amp-s (amp-second) product, b e y o n d which the core will saturate, and the o u t p u t voltage will no longer be a true representation of the current w a v e f o r m to be measured. For the passive a.c.-only probes mentioned, this limits the m a x i m u m current capability at low frequencies; for instance, the Amp-s product for the P6021 with passive t e r m i n a t i o n is 500 x 10 -6 and the same figure applies w h e n using the type 134 amplifier. But this is extended to 0.5 Amp-s w h e n using the current transformer CT-4 with the probe (with or w i t h o u t the amplifier). There is a limit of 100 x 10 -6 Amp-s also for the A6302 d.c. - 50 MHz current probe used with the AM503A current probe amplifier with its 20 A continuous and 50A peak current rating. However, a special feature of the AM503S Current Probe System utilizes the fact that the fluxes due to opposing currents are subtractive. The AM503S senses the current level in the conductor u n d e r test and feeds an equal but opposite current t h r o u g h the probe. This 'bucking current' nulls out the flux due to the current in the transformer and eliminates any core saturation. In the case of the A6303, the bucking current is effective up to a limit of 20A, thus removing any concern for Amp-s product considerations regardless of frequency, except for currents over the 2 0 A continuous rating up to the 50 A peak rating. Difficulty can arise w h e n trying to measure an a.c. signal c o m p o n e n t riding on a larger d.c. standing current. Current bucking can be used with any current probe to circumvent the problem, as indicated in Figure 4.4(b), t h o u g h the highfrequency response m a y suffer as a result, due to the presence of the additional winding. Various current transformers are available to increase the current range that can be measured. For example, the CT-4 extends the range of the P6021 to 20 000 A peak.

Viewing hoods M o d e r n oscilloscopes are generally entirely satisfactory w h e n displaying a repetitive waveform, say a sine wave, or a pulse train with a mark/space ratio near unity. However, if the pulse is

42

Oscilloscopes

n a r r o w a n d t h e r e p e t i t i o n f r e q u e n c y low, for e x a m p l e a I I~S w i d e pulse o c c u r r i n g o n c e e v e r y millisecond, m a n y oscilloscopes o n t h e m a r k e t - especially t h e less e x p e n s i v e o n e s - will not p r o d u c e a b r i g h t e n o u g h p i c t u r e of t h e pulse to be useful. For if t h e t i m e b a s e speed is set to 1 i~s/div, t h e n w i t h t h e usual t e n h o r i z o n t a l divisions, the spot is b l a n k e d for 99 p e r cent of t h e t i m e a n d o n l y d r a w i n g the trace for the r e m a i n i n g 1 per cent. The trace is t h e r e f o r e so d i m as to be invisible, o w i n g to the reflection of a m b i e n t r o o m lighting f r o m t h e t u b e face a n d graticule. A really good v i e w i n g h o o d e n a b l e s the u s e r to v i e w the s c r e e n w h i l e s h u t t i n g o u t all a m b i e n t light. W h e n the eyes b e c o m e darka d a p t e d , e v e n a very faint trace can be seen. The a u t h o r recalls t h a t w i t h t h e aid of its s n u g - f i t t i n g v i e w i n g h o o d the Tektronix 545 oscilloscope, d e s i g n e d in the 1950s, was capable of displaying a 1 i~s pulse o c c u r r i n g o n c e a second. N o w a d a y s of course o n e w o u l d simply w h e e l up a digital storage scope (if one w e r e to h a n d ) , b u t a v i e w i n g h o o d is after all m u c h c h e a p e r !

O s c i l l o s c o p e cameras Besides v i e w i n g a w a v e f o r m , o n e m a y wish to m a k e a p e r m a n e n t record of it, to a p p e a r in a technical report, for e x a m p l e .

Figure 4.5 The PM9381 Polaroid| oscilloscope camera fits Fluke models, providing an instant record. Particularly useful with pure analogue oscilloscopes, which have no screen dump facility (reproduced by courtesy of Fluke Europe BY)

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43

Although tracing paper and a steady h a n d m a y suffice for simple waveforms, an oscilloscope camera was the traditional answer. The major scope manufacturers offered cameras to fit their instruments, but m a n y of the smaller oscilloscope manufacturers did not. Probably the best k n o w n m a n u f a c t u r e r (at least in the UK) of cameras to fit virtually any make of oscilloscope was S h a c k m a n Instruments Ltd. Oscilloscope cameras typically used photographic film with a sensitivity m u c h greater t h a n that of the h u m a n eye, so that a very n a r r o w pulse occurring as a single event could be photographed, even t h o u g h invisible to the naked eye. Figure 4.6 shows the density of the image on a developed film as a function of quantity of light falling on it during the exposure. Gross overexposure can only result in the m a x i m u m density image; gross u n d e r e x p o s u r e results in no image at all. The curve of image density against e x p o s u r e is in fact an S-shaped curve, familiar to all photographers. If the trace to be recorded was so faint that even the fastest film available w o u l d be underexposed, it was still possible to photograph it. This was achieved by deliberately applying an exposure evenly across the whole negative before, during or after

,mage density 1 (maximum) ,

,,

O(m,n,mum) 001

01

correct

10

16o

ex p o s u r e

Figure 4.6

Photographic S curve of image density versus exposure

relative

exposure

44 Oscilloscopes

Figure 4.7 The HM6042 microprocessor-controlled transistor curve tracer displays a set of five curves in the first quadrant. Devices can be compared, for matching, and various 'h' and 'y' parameters calculated (reproduced by courtesy of nameg Ltd)

p h o t o g r a p h i n g the single-event trace. The t e c h n i q u e , k n o w n as 'pre-', ' s i m u l t a n e o u s ' or 'post-' fogging, m o v e s the effective e x p o s u r e from the flat b o t t o m ( u n d e r e x p o s e d ) e n d of the S curve up to t h e steepest central part. It results in the trace appearing on the n e g a t i v e as a slightly d a r k e r line against a m i d - g r e y b a c k g r o u n d - o n the positive print, w h e t h e r p r o d u c e d separately later or 'instantly' as with the Polaroid system, the trace will a p p e a r as a slightly lighter grey line on a m i d - g r e y b a c k g r o u n d . The greatest i m p r o v e m e n t was o b t a i n e d with s i m u l t a n e o u s fogging. Relative to use w i t h o u t fogging, the effective speed of ASA 3000 film (Polaroid types 667, 107, 084 or 47) can be increased by a factor of up to x3, d e p e n d i n g u p o n the film type, scope, c.r.t., c a m e r a and operator. Even g r e a t e r speed is obtainable with ASA 2 0 0 0 0 film (Polaroid type 612). P h o t o g r a p h y using the fogging t e c h n i q u e was a m e a n s of increasing the effective 'writing speed' of an oscilloscope. (Writing speed is a c o n c e p t c o v e r e d m o r e fully in later chapters.) A 'Writing Speed E n h a n c e r ' using the fogging t e c h n i q u e was available for the Tektronix M o d e l C51 'Oscilloscope' Camera,

Accessories

45

w h i c h is n o w discontinued t h o u g h m a n y are still in service. Automatic simultaneous fogging was easily achieved by triggering the e n h a n c e r with the oscilloscope sweep + gate. However, like the camera with which it was designed to be used, this item is rarely encountered, screen shots having been replaced by printouts of a trace captured on a digital storage oscilloscope.

Oscilloscope calibrators These come in varying degrees of complexity. One of the simpler types is often actually incorporated within the better class of oscilloscope. This was particularly necessary in earlier years before the advent of the transistorized oscilloscope, as valves are subject to a steady decline in their characteristics with use. Owing to their usefulness, calibrators of varying degrees of complexity are still incorporated in the more expensive oscilloscopes, often with a choice of several accurate voltage levels at a frequency that is usually 1 kHz to within a few per cent. Also, in some cases a metal loop projecting from the front panel carries a squarewave of current of an accurate value to enable the calibration of current probes to be checked. As a separate accessory, a typical scope calibrator provides a clean squarewave o u t p u t with an accurate peak-to-peak voltage swing or, more usually, a choice of squarewave amplitudes. There m a y also be a choice of frequencies, but if only one is provided it will be of the order of 1 kHz, to enable passive divider probes to be set up as described earlier. The choice of o u t p u t voltage swing enables the Y deflection factor of an oscilloscope to be checked on each range, or at least on all the m o r e sensitive ranges. The more expensive calibrator, such as might be found in an i n s t r u m e n t calibration laboratory, also offers a wide range of accurate squarewave frequencies, say 10 Hz to 10 MHz with intermediate steps in a 1, 2, 5 sequence. This enables the accuracy of an oscilloscope's timebase ranges also to be checked. Figure 4.8 gives the circuit diagram of a simple oscilloscope calibrator that the a u t h o r designed for use with the Practical Wireless 'Purbeck' oscilloscope. It was i n t e n d e d to be p o w e r e d from the 12 V d.c. stabilized supply available at the Purbeck's front panel accessory p o w e r socket, but could be used from any

46 Oscilloscopes

CD 4 0 6 9

i

.F

9

0

lk

1I

-----O

1 165

(150§ 1 MHz

O

47n

0-5 .12v sto b

10 k

from o$(:: 111os(::ope occessory pOwer r~cket

0-2 ----O

01 S---.O 0V

ov i~--o 77~

Figure 4.8 Simple oscilloscope calibrator. The 4.7 kl~ ])reset is adjusted to give a 5V peak-to-peak ()utput" l k H z and 1MHz frequencies are nominal (courtesy

Practical Wireless)

suitable p o w e r source, even a 9V PP9 (6F100, M-1603, 276) b a t t e r y - the much smaller PP3 (6F22, M-1604, 006P, 216) is not r e c o m m e n d e d for this purpose. The preset potentiometer is set so that the m a x i m u m output swing is exactly 5 V peak to peak.

Special graticules, etc. All oscilloscopes nowadays incorporate a graticule, ruled in square divisions, usually ten horizontal divisions by s i x - or more c o m m o n l y e i g h t - vertical ones. On oscilloscopes with a cathode

Accessories

47

Figure 4.9 The OX803B provides a 40MHz bandwidth and sensitivities right down to 1 mV/div. The optional RS232 kit, including series lead and diskette with LabWindows drivers and control software, permits remote control of the instrument with a virtual front panel on the host PC (reproduced by courtesy of Chauvin Arnoux UK Ltd)

ray tube of 13 cm (5 inches) diameter (or diagonal, in the case of the increasingly popular rectangular screen tubes), these divisions are centimetre squares. In addition to the square graticule rulings, most oscilloscopes have horizontal dotted lines across the graticule at 2~ divisions above and below the centreline. If the top and b o t t o m edges of a pulse or squarewave are aligned with these, the rulings 2 divisions above and below the centreline intersect the edges of the pulse at the 10 per cent and 90 per cent points, m a k i n g it easy to m e a s u r e t h e rise and fall times, as illustrated in Figure 10.4. More expensive oscilloscopes have variable intensity edge lighting of the graticule divisions, w h i c h helps m a k e t h e m stand out. This is especially useful w h e n p h o t o g r a p h i n g a w a v e f o r m as the camera h o o d excludes a m b i e n t lighting; the graticule w o u l d therefore not be recorded. In addition, there is a transparent sheet of Perspex or similar material in front of the tube, tinted the same colour as the c.r.t.'s trace. This tinted sheet m a y have the graticule divisions m a r k e d u p o n its rear surface. Alternatively, in m a n y scopes the graticule is printed on the inside of the c.r.t. screen before the p h o s p h o r is applied; this completely eliminates parallax b e t w e e n the trace and the graticule, but of course makes

48

Oscilloscopes

it i m p o s s i b l e to r e m o v e t h e latter w h e n it is desired to use a d i f f e r e n t graticule. The p u r p o s e of t h e t i n t e d s h e e t is to i m p r o v e the c o n t r a s t b e t w e e n t h e trace a n d t h e rest of t h e screen. The b r i g h t n e s s of t h e trace is r e d u c e d s o m e w h a t b y t h e t i n t e d sheet, b u t the trace's light o n l y has to pass t h r o u g h t h e s h e e t o n c e . A m b i e n t light, o n t h e o t h e r h a n d , is a t t e n u a t e d as it passes t h r o u g h t h e s h e e t b e f o r e b e i n g r e f l e c t e d f r o m t h e c.r.t, screen, a n d a t t e n u a t e d a g a i n as it passes out, r e s u l t i n g in i m p r o v e d c o n t r a s t . The i m p r o v e m e n t is e v e n g r e a t e r for c o l o u r s d i f f e r e n t f r o m t h a t of t h e trace. Increasingly, a n e u t r a l g r e y - t i n t e d s h e e t is u s e d in place of o n e t h e s a m e c o l o u r as t h e trace. The m a t e r i a l is a special plastic s h e e t w i t h t h e p r o p e r t y of circularly p o l a r i z i n g light w h i c h passes t h r o u g h it. The trace is little a t t e n u a t e d , b e c a u s e it is initially u n p o l a r i z e d a n d o n l y passes t h r o u g h t h e filter once, b u t a m b i e n t

Figure 4.10 The VC-7502 dual channel 100Ms/s digital storage oscilloscope provides a 150 MHz bandwidth. GPIB and RS232 are standard, and IEEE-defined pulse parameter measurements can be automatically measured. The VC-7504 is similar but has four channels (reproduced by courtesy of Hitachi Denshi (UK) Ltd)

Accessories 49 light falling o n t h e s c r e e n of t h e c.r.t, is circularly polarized. U p o n reflection, its circular p o l a r i z a t i o n is n o w of t h e w r o n g h a n d to pass b a c k t h r o u g h t h e filter, r e s u l t i n g in m u c h i m p r o v e d contrast. In p a r t i c u l a r l y b r i g h t s u r r o u n d i n g s a m e s h filter c a n be used. This is a fine m e t a l m e s h f i n i s h e d in m a t t black; it r e d u c e s t h e b r i g h t n e s s of t h e trace by a b o u t a q u a r t e r , b u t p r o v i d e s v e r y h i g h a t t e n u a t i o n of a m b i e n t light reflections. Special graticules h a v e b e e n d e v e l o p e d for fitting to a n oscilloscope in place of t h e s t a n d a r d o n e . A typical e x a m p l e is a graticule w i t h n o m i n a l a n d limit m a r k i n g s for a s i n e - s q u a r e d p u l s e - a n d - b a r test w a v e f o r m , u s e d for t e s t i n g t e l e v i s i o n e q u i p m e n t r e s p o n s e t i m e s a n d differential g a i n a n d p h a s e . S m i t h c h a r t a n d p o l a r graticules are also available, b u t t h e s e are g e n e r a l l y u s e d w i t h a s p e c i a l - p u r p o s e oscilloscope display f o r m i n g p a r t of a n e t w o r k analyser.

M a i n s isolation The Y i n p u t sockets o n a n oscilloscope n o r m a l l y h a v e t h e i r o u t e r s c r e e n s c o n n e c t e d to t h e i n s t r u m e n t ' s m e t a l w o r k a n d t h u s to t h e e a r t h w i r e in t h e m a i n s lead. Thus t h e i n p u t as it stands c a n n o t be c o n n e c t e d to circuitry w h i c h is at a d i f f e r e n t p o t e n t i a l f r o m m a i n s

Figure 4.I1 Showing typical scale-factor readouts on a modern high performance oscilloscope - the PM3094 featured in Chapter 3. (a) A typical measurement application, with the Delta Time cursors in use. The measurement is displayed as both period and frequency. (b) A (main) and B (delayed) timebases in use. The highlighted portion of the A trace is displayed on the lower delayed trace, which starts 180.0 p~s later than the main trace

50 Oscilloscopes

Figure 4.12 100 Base T signal testing with standard communications mask, on a TDS instrument from the Tektronix range (courtesy Tektronix UK Ltd)

earth, for e x a m p l e live-side c o m p o n e n t s in a direct-off-line s w i t c h m o d e p o w e r supply. Hence the highly deprecated and very d a n g e r o u s practice of disconnecting an oscilloscope's earth lead. However, u n d e r specific conditions, safety standards do p e r m i t indirect g r o u n d i n g as an alternative to direct grounding. All of the g r o u n d i n g r e q u i r e m e n t s apply, except that the g r o u n d i n g circuit need not be completed until the available voltage or c u r r e n t exceeds a prescribed a m o u n t . The Tektronix A6901 G r o u n d Isolation M o n i t o r fits b e t w e e n an oscilloscope and the mains, a n d cr m o n i t o r s the w~ltage on the instrument's case/ m e t a l w o r k . The latter is permitted to float up to 40 V peak, 28 V rms from ground. W h e n this value is exceeded the mains supply to the i n s t r u m e n t is interrupted, the isolated g r o u n d i n g system is c o n n e c t e d to the supply g r o u n d i n g system, and an audible alarm is sounded. Applications include connecting the oscilloscope g r o u n d to t h e - 2 V l o a d - r e t u r n reference rail instead of zero volts in ECL circuits to reduce probe loading, and reducing h u m problems in low-level audio circuits by aw~iding earth lr An alternative approach to m a i n s isolation is to disconnect the mains lead entirely. The Tektronix models 222A, 222PS and 224 can operate for typically four to six hours from internal sealed lead/acid batteries, or suitable external d.c. or a.c. supplies. Of double-insulated, impact-resistant, plastic construction, these oscilloscopes w h e n operated from their internal batteries can be

Accessories

51

floated at up to +850 V d.c. plus peak a.c. above or below g r o u n d (+400 V in the case of the 222 A). Although discontinued, these items appear from time to time on the second user market, very modestly priced, and can therefore be w o r t h acquiring w h e r e offearth m e a s u r e m e n t s m u s t be made. Normal safety rules should always be observed w h e n working with high voltages, especially w h e r e the g r o u n d lead of the probe is at other t h a n earth potential. It is unwise to w o r k on e q u i p m e n t w i t h voltages in excess of 50V if there is n o other person in the same area. Yet a n o t h e r alternative is signal voltage isolation. This is covered in the next chapter.

5

Using oscilloscopes It s e e m superfluous to say that, whe n using a n oscilloscope to view a waveform, one should choose a n instrument appropriate to the ,job in hand. Yet, as explained in the course of this chapter, besides the more obvious requirements ('does it have a bandwidth wide enough to display my signal faithfully?', 'is it sensitive enough to see the very small signal I wish to view?') there are quite a few other considerations that are a little less obvious. Some have already been pointed out, notably in Chapter 3, and others will become apparent in the course of this chapter. We shall also consider t h e case where there is no choice and one is faced with the task of trying t o obtain some useful information about a waveform with a n oscilloscope which is hardly adequare for the purpose. Use of probes ()iiestions t h a t people HC'W t o using oscilloscopes oftcn ask arc: ' D o 1 always need a probe? If not, how do 1 know when 1.0use one and w h r n not?' The first part of Chapter 4 should havc

provided a good deal of' insight into this: if you a r e still p u ~ ~ 1 t il. d might be worth reading again. B u t for a short, simple answer, the author's advice is always t o use a 1 O : l passive divider probe (correctly set up for the oscilloscope you are using) as a matter of habit. If. owing to the attendant attenuation factor of 10, the signal y o u wish to view gives insufficient vertical deflcction even with the Y input setting a t its most sensitive position, then it will be necessary to consider whether i t is possible to depart from your standard practice o f using such a probe. For example, if you are using a metre or so of general-purpose, audio screened lead t o connect the signal t o be viewed to the oscilloscopc, the total capacitivc loading on thc circuit may wcIl be scvcrnl hundrcd picofarads. This will he of no consequence if looking at, say, t h e secondary voltage of a mains transformer, a n d gerierally acceptable for viewing the output of a hi-fi amplilier over the whole a u d i o range. However, 200 pF has a reactance of

Using oscilloscopes 53 40 k ~ at 20 kHz, and you might well get a misleading picture of a test w a v e f o r m in one of the earlier high-impedance stages of the amplifier; worse, the phase shift caused by the additional capacitance could cause the amplifier to oscillate if the phase margin of its negative feedback loop is rather sparse. Yet it is precisely in the earlier small-signal stages that you might w a n t to avoid the a t t e n u a t i o n of a passive divider probe. Two courses of action are open: 75 f~ coaxial cable as used for television aerial downleads, for example, has a capacitance of approximately 60 pF/metre, as against 1 5 0 - 1 8 0 p F / m e t r e for an audio screened lead. So if the connection to the scope can be made with a mere half metre of coax, the total capacitive input loading including the oscilloscope's input capacitance can be kept d o w n to less t h a n 60pF. Alternatively, an active probe as described in Chapter 4 m a y provide the answer. W h e n investigating circuits operating at r.f. a passive divider probe is essential. Even with it, care must be taken if misleading results are to be avoided. For example, if a probe is connected across a t u n e d circuit, the extra 1 0 - 1 2 p F loading of the probe will change the resonant frequency to some extent. How m u c h depends u p o n h o w m u c h capacitance there is in parallel w i t h the inductor to start with, but the probe's capacitance will be quite e n o u g h to upset the response of a conventional d o u b l e - t u n e d i.f. stage, resulting in the w r o n g amplitude being displayed u p o n the screen. The effect on an oscillator can be m u c h m o r e dire; not only will the connection of a probe change the oscillator's frequency, it will generally cause a reduction in amplitude as well, and m a y very likely stop the oscillator altogether. T h e reason for this is that the impedance seen 'looking into' the probe is 10Mf~ at d.c. only, and falls with frequency (see Figure 4.3). At several MHz it m a y be d o w n to a few h u n d r e d kilohms or even lower, imposing damping on the t u n e d circuit to w h i c h it is connected. In the case of an oscillator, of course, there will generally be several volts peak to peak of signal available, so if the oscilloscope is reasonably sensitive (i.e. has a 5 or 1 0 m V / d i v range) it will be possible to use a x l00 probe with an input capacitance of about 1 pF. If a x l 0 probe is all that is available, it is possible to achieve m u c h the same result by connecting a 1.2 pF

54 Oscilloscopes capacitor in series with the probe tip. The result will be a sort of x100 probe that is not exactly calibrated and will not work at low frequencies. However, it will permit you to m o n i t o r oscillators, and t u n e d circuits generally, w i t h o u t affecting t h e m unduly. In fact if it is only required to m o n i t o r the frequency and waveshape of the oscillator, the 1.2pF capacitor can be dispensed with entirely and the tip of the xl 0 probe simply held very close to, but not actually touching, the tuned circuit.

Trace finding W h e n using an oscilloscope to view waveforms, you will generally have some idea of w h a t to expect. Thus, if examining TTL or CMOS logic gates operating at a clock frequency of 1 MHz, you w o u l d use a x l0 divider probe and set the scope's Y sensitivity to 0.1 or 0.2 V/div, d.c. coupled, giving a 1 or 2 V/div sensitivity on the screen. The timebase speed would be set to, say, 1 b~s/div. However, it can happen that you do not k n o w the appropriate settings, either because of lack of information on the circuit u n d e r test, or because owing to a fault the waveform is not w h a t you w o u l d expect. Some scopes (e.g. that featured in Chapter 3) have an 'auto everything' feature, which will test the peak-topeak amplitude of the input signal and select a suitable Y sensitivity range, also checking the frequency or repetition rate of the input waveform and selecting a suitable timebase speed to show several complete cycles. Such an oscilloscope is very h a n d y for a technician of limited experience, or a repair m a n faultfinding on a complicated piece of equipment, though certain types of w a v e f o r m s - those with an extreme m a r k / s p a c e ratio or m a n y high-frequency c o m p o n e n t s can result in a nono p t i m u m display. But the majority of oscilloscopes do not have this feature. Let us suppose, then, that w h e n the input signal is connected, the trace disappears from the screen of the oscilloscope. The more expensive type of scope (and increasingly n o w a d a y s the cheaper models also) will have a trace finder button: pressing this has the effect of restoring the trace to the screen regardless of the control settings, albeit in a defocused form. But its use should become unnecessary w h e n you k n o w h o w to drive an oscilloscope properly.

Using oscilloscopes 55 The c o m m o n e s t cause of a 'lost trace' is c o n n e c t i n g a signal with a large d.c. c o m p o n e n t to the scope w i t h the Y i n p u t d.c. coupled a n d the i n p u t a t t e n u a t o r at too sensitive a setting. So if you don't k n o w w h a t to expect, set the trace to the centre of the screen, set the Y i n p u t to a.c. coupled a n d the i n p u t a t t e n u a t o r to the least sensitive s e t t i n g - usually 20 or 50V/div. It will t h e n n e e d a very large signal voltage to lose the trace, especially if using a 10:1 probe! In fact, w i t h a.c. coupling, c o n n e c t i n g a large d.c. voltage will m o v e the trace up (or of course d o w n , if the voltage is negative), but the trace will t h e n slowly r e t u r n to the centre of the screen. This is so e v e n if the a t t e n u a t o r is at one of its m o r e sensitive positions, a l t h o u g h in this case it could take m a n y seconds before the trace r e t u r n s to the screen. You can still lose the trace e v e n w i t h the Y i n p u t a.c. coupled, if the i n p u t a t t e n u a t o r is at too sensitive a setting. Take, for example, a 1 kHz TTL s q u a r e w a v e a.c. coupled to an oscilloscope set to a sensitivity of 5 mV/div: e v e n using a 10:1 probe, the tops of the w a v e f o r m will be off the top of the screen a n d the b o t t o m s b e l o w the b o t t o m edge of the screen. A l t h o u g h parts of the rising a n d falling edges will be on-screen, t h e y will be so rapid as to leave too faint a trace to be seen. If the scope has a trace-finder or locate b u t t o n , pressing this will s h o w lines of dashes n e a r the top a n d b o t t o m of the screen, but if y o u always follow the s o u n d practice of setting the Y i n p u t to an a p p r o p r i a t e setting if k n o w n , or to the least sensitive setting if not k n o w n , y o u n e e d n e v e r lose the trace in the first place. The trace can also be lost t h r o u g h i n a p p r o p r i a t e settings of the X timebase controls. Suppose, for example, t h a t y o u apply a 100 Hz sine w a v e to an oscilloscope, w i t h suitable settings of the Y i n p u t controls but w i t h the timebase speed set to 1 ~s/div. W h e n the timebase triggers the trace will be complete in 10 ~s (assuming the screen has 10 horizontal divisions). At the e n d of the s w e e p the trace will r e m a i n b l a n k e d for the n e x t 9.99 ms until triggered by the n e x t cycle; see Figure 5.1. With the trace b l a n k e d for 99.9 per cent of the time, it will be invisible, a n d on m a n y c h e a p e r scopes will r e m a i n so e v e n if the intensity control is t u r n e d up. Only oscilloscopes w i t h a high writing speed (see C h a p t e r 9) will cope w i t h this situation. The rule therefore is t h a t if y o u do n o t k n o w

56 Oscilloscopes

Figure 5.1 100Hz sine wave displayed with l l~s/div sweep speed. The 10t~s segment is not to scale, having been exaggerated for clarity. The display shows one-thousandth of a cycle, which would in practice be too dim to see

t h e f r e q u e n c y of t h e w a v e f o r m y o u w i s h to e x a m i n e , set t h e t i m e b a s e s p e e d to o n e of its s l o w e r positions, say 2 ms/div. This leaves just o n e tricky case to w a t c h o u t for: a n a r r o w p u l s e o c c u r r i n g at a low r e p e t i t i o n rate, say lOOns w i d e at 1 0 0 p p s (pulses p e r s e c o n d ) . At 2 m s / d i v s w e e p s p e e d t h e pulses will be too n a r r o w to see a n d t h e trace will a p p e a r i n d i s t i n g u i s h a b l e f r o m t h e straight line p r o d u c e d by t h e a u t o b r i g h t l i n e circuit. The test h e r e is s i m p l y to switch to n o r m a l trigger, w h i c h disables t h e b r i g h t l i n e circuit. N o w t h e trace will o n l y a p p e a r w h e n t h e trigger c o n t r o l is set to t h a t part of its travel c o v e r e d by t h e i n p u t pulse.

Using oscilloscopes 57

Practical examples Having looked at the dos a n d don'ts of connecting a signal to an oscilloscope, let's consider some practical m e a s u r e m e n t situations and see w h a t t h e y involve, starting w i t h a simple case.

Example 1 Suppose y o u wish to look at the supply rail of a transistor amplifier to see just h o w m u c h 100Hz ripple there is. The amplifier probably has t w o supply rails, say +24 V a n d - 2 4 V, so if y o u set the trace to the centre of the screen w i t h the Y shift control and select 1V/div setting, d.c. coupled, t h e n w i t h a 10:1 probe c o n n e c t e d to one supply rail the trace will m o v e up or d o w n 2.4 divisions. (All the examples assume a graticule f o r m a t of ten horizontal by eight vertical divisions.) Most transistor amplifiers n o w a d a y s operate in class B, w h i c h m e a n s that w i t h the v o l u m e t u r n e d d o w n comparatively little c u r r e n t is d r a w n from the p o w e r supply. The +2.4 division vertical deflections will reveal that the supplies are indeed plus a n d m i n u s 24 V, but the trace will almost certainly look exactly like a straight line. If y o u wish to see the ripple, the Y i n p u t sensitivity m u s t be increased. If y o u increase it to 0.5 V/div (effectively 5 V/div in view of the probe) the trace will m o v e off-screen. True, y o u can probably get it back w i t h the aid of the Y shift control, but the ripple will still be too small to see a n d too small to trigger the timebase. The a n s w e r is of course to set the Y i n p u t to a.c. coupled, as this will block the d.c. voltage. You can n o w increase the Y input sensitivity as m u c h as y o u like. With a 2 m s / d i v timebase speed y o u should see two complete cycles of ripple as in Figure 5.2 (a). With a simple repetitive w a v e f o r m like this, a l t h o u g h the n o r m a l triggering m o d e can be used if desired, triggering in the auto m o d e s h o u l d be entirely satisfactory, p r o v i d e d there is e n o u g h Y gain available to give one division or so vertical deflection. If there isn't, this a good e x a m p l e of a case w h e r e y o u can happily omit the 10:1 divider probe a n d simply use a screened lead. In the auto trigger mode, the trigger circuit is a.c. coupled, so triggering will occur e v e n for a fairly small w a v e f o r m regardless

58 Oscilloscopes

Figure 5.2 Ripple waveform across power-supply smoothing capacitor. (a) Fullwave or bridge circuit. (b) As (a) but with faulty diode, or half-wave circuit. Horizontal scale 2 ms/div

of w h e t h e r the trace is n e a r t h e top of t h e screen or n e a r t h e b o t t o m , i.e. regardless of t h e d.c. c o m p o n e n t . It t h e r e f o r e follows t h a t t h e r e is a f r e q u e n c y b e l o w w h i c h t h e a u t o trigger m o d e b e c o m e s p r o g r e s s i v e l y less sensitive. D e p e n d i n g on t h e p a r t i c u l a r oscilloscope design, this is u s u a l l y in t h e r a n g e 10 to 50 Hz. W h e n e x a m i n i n g w a v e f o r m s of a f r e q u e n c y m u c h l o w e r t h a n this, a u t o t r i g g e r i n g will n o t be effective, b e c a u s e t h e a u t o trigger circuit will r e t r i g g e r t h e t i m e b a s e in o r d e r to p r o v i d e t h e ' a u t o

Using oscilloscopes 59 brightline' before the next trigger pulse arrives. Thus the display will not be synchronized. In this case, m a n u a l trigger, d.c. coupled, should be selected, and of course the Y input m u s t also be set to d.c. coupled. This m e a n s that if one wishes to e x a m i n e a low frequency of very small amplitude, riding on a large d.c. component, one has problems. However, referring to Figure 5.2, auto trigger is ideal for the purpose of checking for 100Hz supply line ripple. In the auto mode, in the absence of a Y input big e n o u g h to trigger the trace, circuitry internal to the oscilloscope will (on virtually all makes and models) cause the timebase to r u n repetitively. This results in the brightline on the screen, avoiding a lost trace in the absence of a Y input. If the w a v e f o r m is like Figure 5.2 (b) this reveals straight a w a y that one of the diodes in the p o w e r supply's bridge rectifier is faulty. W i t h o u t an oscilloscope you m i g h t by deduction have suspected this, but to confirm it you w o u l d have had to disconnect components. If the bridge rectifier is (as is likely) a single c o m p o n e n t rather t h a n four separate p o w e r diodes, this is even more complicated, but w i t h an oscilloscope the diagnosis is easy.

Example 2 Now consider a slightly more complex case. Suppose you wish to e x a m i n e the waveforms produced by a TTL decade divider such as an SN74LS90 r u n n i n g at a fairly high clock rate. The various waveforms are as s h o w n in Figure 5.3. The input w a v e f o r m and the o u t p u t waveforms of the first, third and fourth stages are all simple, repetitive waveforms (although only the input and the first stage o u t p u t waveforms are squarewaves in the sense of having a unity m a r k / s p a c e ratio): so w i t h any appropriate timebase speed there will be no p r o b l e m in triggering, either using n o r m a l trigger or in the auto mode. However, the QB o u t p u t from the second divider stage is a little more tricky. Using internal triggering as has b e e n a s s u m e d up to now, bear in m i n d that, depending on the clock frequency and the timebase speed, if one trace c o m m e n c e s at point 1 (positivegoing trigger selected) it could t e r m i n a t e at point 2 (thus displaying rather m o r e t h a n one complete cycle of the QB

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Using oscilloscopes 61 w a v e f o r m ) a n d trigger again at point 3. The section of the w a v e f o r m displayed on this scan w o u l d thus be displaced horizontally relative to the previous scan, w i t h the result s h o w n in Figure 5.4. There are a n u m b e r of w a y s r o u n d this problem, d e p e n d i n g on the facilities available on the scope y o u are using. Consider first a very basic scope, a n d a s s u m e also that y o u c a n n o t c h a n g e the w a v e f o r m ' s clock frequency. If the scope has a c o n t i n u o u s l y variable timebase control, y o u can use this to set a slightly slower timebase speed so that the trace t e r m i n a t e s just after point 3. The n e x t sweep will t h e n c o m m e n c e at the n e x t point I, a n d an u n a m b i g u o u s display will result. There are t w o snags to this solution, h o w e v e r . First, the timebase is n o w uncalibrated, w h i c h is i n c o n v e n i e n t ; second, m a n y i n e x p e n s i v e scopes do not provide a variable timebase speed control. But every scope, e v e n the cheapest, has an e x t e r n a l trigger input, so the s t r a i g h t f o r w a r d solution is to apply the QD w a v e f o r m to this. On a dual trace display scope one can alternatively display the QB trace on one Y i n p u t a n d the QD w a v e f o r m on the other, w i t h internal triggering f r o m the latter selected. If it is particularly desired to display the clock a n d the QB w a v e f o r m s s i m u l t a n e o u s l y on a dual trace scope (for e x a m p l e , w h e n m e a s u r i n g the p r o p a g a t i o n delay t h r o u g h the first t w o

Figure 5.4 QB trace overlapped owing to triggering at points 1 and 3 (see Figure 5.3) alternately

62

Oscilloscopes

stages of the counter), applying t.he Q n waveform to the exterm1 trigger input is again appropriate. Of coursc it involvcs making an ext.ra connect.iori tielween the oscilloscope and the circuit. under test, but even this minor inconvenience can be avoided if the scope has a trigger hold-off control. Trigger hold-oIf was mentioned in Chapter 3 and is a very useful facility in this situation. Normally a n oscilloscope's timebase is avaihble to be retriggered as soon as the fryback following the scan is completed. and this is the case when the hold-off control is in the normal (fully anticlockwise) position. As it is rotated further clockwise there is a n increasing delay between the end of the flyback and the time the trace is next available to be retriggered. The maximum delay o r hold-off is generally several times (up to lox) the sweep time, depending o n the make of oscilloscope. With this control it is thus possible to obtain a stable display using internal triggering from the Q R waveform with the timebase speed at any calibrated setting, regardless of the clock frequency. M u n u d trigg~rin~q Rearing in mind t h y above points, manual triggering frvrri waveforms cii.hrr digital or sinusoirlal is straightl'orward: simply

select manual triggcr, positivc o r negative trigger polarity R S required, and adjust the trigger level control t o cause the m c e to commence a t the desired level on the chosen edge of the waveform. Triggcring from, say, the positive-going edge of a sine wave will then he possible from a point slightly above the negative peak, rig111 rip almost to the positive peak. The exception is when examining fairly low frequencies with thc 1.f. reject trigger facility in use, o r fairly high frequencies with h.f. reject in use. Thesc controls cause a progressive decrease in sensitivity at low and high frequencies respectively: their use is covered in Chapter 3 . Besides decreasing the effect of unwanted low- or high-frequency components on triggering from the wanted wavcform, thcsc controls have an incidental dfcct o n rriggering that is worth noting. Suppost. you arc usiiig h.1. reject o n ari oscilloscope where this mode rolls off the high-frequency response o f the trigger channel a h v c S O kHz, in ordcr t o ohaiii a slablc display of a 50 kHz sine

using oscilloscopes 63 wave that has superimposed some low-level n a r r o w spikes of an unrelated frequency. The trigger circuit will n o w reject the spikes and respond only to the w a n t e d 50 kHz sine wave, which will thus be cleanly locked although the spikes may be visible r u n n i n g through. If very narrow, they m a y well be quite invisible at the timebase speed used to view the w a n t e d 50kHz signal, yet w i t h o u t the h.f. reject facility they could have made it quite impossible to obtain a locked picture of the w a n t e d signal. Now the trigger circuit will respond to the w a n t e d 50 kHz sine wave, although its response will be 3 dB down, i.e. the smallest 50 kHz sine wave which it will lock on is about 40 per cent larger t h a n at m u c h lower frequencies (assuming that the h.f. or 1.f. reject filters are simple single pole types, as is usual). In addition, there will be a corresponding 45 ~ phase lag in the trigger channel. The significance of this is that if you have selected m a n u a l trigger, positive-going, the trigger level control will no longer enable you to trigger at any desired level on the positive-going flank of the sine wave. Instead, the trigger level control will initiate the sweep a n y w h e r e from (just above) one-quarter of the way up the positive flank to almost one-quarter of the w a y d o w n the following negative-going flank. At frequencies higher t h a n 50 kHz, this effect will become even more pronounced. A similar effect will be noted w h e n triggering from a w a v e f o r m near the 1.f. reject cut-off frequency with 1.f. reject selected, except that in this case there will be a phase advance, so the trigger range will be advanced by up to a quarter of a cycle or even more, rather t h a n retarded as in the h.f. reject case. Trigger circuitry in digital storage oscilloscopes (and especially in logic analysers) often offers more functionality t h a n that found in straightforward analogue oscilloscopes. Figure 5.5(a) shows the effect of w i n d o w triggering, which is useful for catching glitches or overvoltage conditions. Usually, each level is independently settable by the user. Figure 5.5(b) shows hysteresis triggering, which makes the trigger point less susceptible to noise. It allows a level-and-slope trigger to occur only after the signal has crossed a hysteresis level. This level acts as a trigger enable. Glitch triggering monitors the signal for pulses less t h a n a specified width. The width is user selectable. In a DSO,

64

Oscilloscopes

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(b) Figure 5.5 In addition to a straightforward choice of level and polarity (perhaps with h.f. or 1.f. reject), some oscilloscopes offer a variety of other triggering modes. Two are illustrated here. W i n d o w triggering is useful in a DSO in 'babysitting' mode, waiting to capture an elusive glitch, whilst hysteresis triggering can help with triggering on a noisy signal (courtesy LeCroy Ltd)

Using oscilloscopes

65

independent glitch trigger circuits can offer triggering on widths less than the digitizing sample interval. On the other hand, interval triggering monitors the signal for pulses wider than a specified width. The width is user selectable. It is useful for capturing signal drop-outs. Delay by time ('A delayed by B') was discussed in connection with analogue scopes in Chapter 3. M a n y DSOs offer both delay by time and delay by events, permitting the user to view in detail specific w a v e f o r m sections w i t h o u t extreme lengths of waveform memory. It is especially useful in conjunction with pattern triggering for testing digital systems. Pattern triggering lets the user select levels and slopes for several inputs. A trigger occurs only w h e n all conditions are simultaneously met. U s e of dual trace s c o p e s

It is frequently convenient, and indeed essential, to be able to view two waveforms simultaneously. This facility has been available in scopes near the top end of the market since before the Second World War, in, for example, the forerunners of the oscilloscope illustrated in the frontispiece (p. xii). However, for m a n y years the means of achieving this was to use a cathode ray tube with two beams, each with its o w n Y deflection system but sharing c o m m o n X deflection plates. The two beams could be produced by two i n d e p e n d e n t electron gun assemblies, or by a single gun and a 'splitter plate' to slice the b e a m in half. With an oscilloscope using this type of dual trace operation, k n o w n as a 'dual-beam' oscilloscope, one could always be certain that the two waveforms viewed really were in the time (or phase) relationship shown, since both beams were deflected simultaneously by the c o m m o n X timebase waveform. Stemming from the advances in electronic circuitry made during the Second World War in connection with radar displays, it became possible to use a single b e a m cathode ray tube to display two (or more) traces. The resultant simplification of the cathode ray tube enabled designers to concentrate on producing tubes with higher writing speed and greater deflection sensitivity, especially in the Y axis. The importance of this to the evolution of oscilloscopes with better performance generally and wider

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bandwidth in particular cannot be overcstirnated and is covered in iiiore det.ail in CIiapt.ei-s9 and 10, but. the retiirn t.o single beam tubes has particular significance whc n using a dual tracc scope to exarnixi.e the relative tirriirig of two wavcl'orrns. To diqplay two waveforms, the single beam must somehow be shared between the Y 1 arid Y2 traces. Dual trace oscilloscopes almost invariably offer a front panel selectable choice of aIternate and chopped modes as well as Y 1 only and Y 2 o n l y as described in Chapter 3 . Likewise, there is usually a choice of triggering source: Y1, Y 2 , mixed (sometimes called 'normal'), o r external. The chopped mode of display writes both the traces during each single sweep. It achieves this by writing a very short portion of the Y 1 trace, then a portion of the Y 2 trace and s o on alternately. Each trace therefore consists of a series of short dashes, but when displaying low-frequency signals the dashes merge t o provide the apprarance of t.wo continuous traces. Compared with the alternarc modc, where first a complete Y 1 trace is written a n d t.hrn a s r c o n d s w w p wriles rhe Y 2 tracc. thc chopped mode results iri thc abscncc of flickel- down t o hall' r l i c . swecp rrpetition rate at. which llickrr appears in the altrrnatc modc. On t h e other harid, wlieri displayirig lrcquericics of a few 0 1 - rriaiiy kilohertz, rhr dotted line structiirc o l the traces i n tht: rliopprd mode may hecomc apparcnr as the chopping Tale is grncmlly between 100 kHz arid a Iew MHz. Thus the choppcd inode i s mos1 suitable for low-frequency signals and thc altcmatc inode tor higher frequency signals, say a lew kilohertz iipwards. For 'single shot' operation, for examplc when photographing the screen to record what happens at two points in a circuit l'ollowing the operation o l a push button, the choppcd mode is obviously appropriate, since in the alternate mode only one of the two traces will appear. I f the signals to bc observed are such as t o require a rimebasc speed too high for ttir chopped mode to he useful. then i t is impossible with a dual trace real-time analogue oscilloscope t o observe both channcls o n a single shot basis, a limitation that did n o t apply t o the oldcr, fruc dual hcam oscilloscopcs si.ich as that illListratcd i n thc lrontispicce. The Could OS.260, long discontinucd, was p r o h h l y thc last, srriall, budgel-pricc4, true dual lwarn oscilloscope on thc market. The

Using oscilloscopes 67 last true d u a l - b e a m oscilloscopes available in the higher price range were the Tektronix models 7844 (400 MHz bandwidth) and the 5113 (bistable storage), both n o w discontinued. The need for such oscilloscopes has been o v e r t a k e n by improved models of Digital Storage Oscilloscopes, w h i c h can acquire two waveforms simultaneously (or more, depending on the n u m b e r of input channels) on a single shot basis. The various time records are thus inherently c o n t e m p o r a n e o u s . The exception is a two or four channel DSO where, for cheapness, a single high speed DAC is used. W h e n using two or four channels at the m a x i m u m sampling rate, the DAC converts the signal in each channel in turn, resulting in a half or a quarter of the digitizing rate per channel c o m p a r e d with that available w h e n using one channel alone. The resultant time records are thus displaced by multiples of the period b e t w e e n samples - by 1 ns in the case of a 1 Gs/s ADC. This m a y become apparent w h e n viewing the resultant stored waveforms with X axis (time) expansion. It was stated earlier that in the chopped mode, for signals above a few kilohertz, the dotted line structure may b e c o m e apparent. However, in general there will be no fixed frequency relation b e t w e e n the signal being viewed (to w h i c h the trace repetition frequency is locked) and the chopping frequency: so the missing portions of the Y1 trace on one sweep, w h e r e the b e a m is writing parts of the Y2 trace, will be partly or completely filled in on the next sweep, and so on. Given an a.f. (audio frequency) oscillator with a good slow-motion dial drive though, it is quite an easy m a t t e r to adjust its o u t p u t at a r o u n d 10 kHz to a s u b h a r m o n i c of the chopping frequency. As the right frequency is approached, the dashes of w h i c h each trace is composed can be seen r u n n i n g across the trace, and w i t h a little care (and a stable oscillator) they can be m a d e stationary. The slightest m i s t u n i n g should cause t h e m to r u n through, to left or to right. On some oscilloscopes, they will stay locked with very slight mistuning, but this is a sign of poor design or construction, resulting in crosstalk b e t w e e n the chopping frequency generator and the trigger circuitry. This will not be the case on most w e l l - k n o w n makes of oscilloscope; w h e n the signal and the chopping frequency are not related, as is usually the case in practice, the chopped m o d e can be used for

68

Oscilloscopes

repetitive waveforms right u p to and beyond the chopping frquency, though there is little point in so doing. The choice of trigger source is very important when working with a dual trace oscilloscupe. As mentioned earlier when discussing the waveforrns encountered in a decade divider stage, if the frcqucncics being displayed on the Y1 and Y 2 t.races are different b t . ~ ~relat.ed, . one should trigger from the lower frcqurncy, whcthcr it be displaycd on the Y 1 o r the Y 2 (.race. Dual trace scopes usually have a 'mixed trigger' facility; this Incans that when used in the alternate mode with internal triggering, the sweep will be triggered from the Y 1 channel when displaying thc Y 1 trace, but on the next sweep will display the Y2 signal triggered from the Y 2 channel. Consequently both traces will be perfectly synchronized with their respective displayed signals and the traces will appear t o have a fixed stable relationship. In fact, the signals displayed on the two channels could have totally unrelated frequencies, as would he apparent if triggering from Y 1 were selected, in which case the Y 2 trace would not be synchronized, and vice versa. In the mixed triggering mode in fact, the oscilloscope is simply equivalent to two entirely separate single channel scopes, each internally triggered I r c m its o w i signal. Nevertheless, mixed ~riggeringcan bc very uselul l o r keeping a n eye o n two unrelated wavetornis s i m u l ta nc ~ot~sl~, prrividcd this fact is borne firmly in mind. C a r e is nccded even when ihc two Irc~quencics arc ha rm() r i ica 1 Iy re la 1c d o r idc n t ica I. M i x cd t riggcri ng w i I1 show the 0" reference oiitpLit a n d the 90" q t i d r a l u r c outpu.t of a quadratiirc oscillator as bcirig i i i phase, whereas triggering from the reference input will show the correcL 90" phase diflerence between the two sine wavcs. The moral is t o use mixed triggering only whcn i t is specifically required. a n d to regard the selection of the appropriate triggering arrangements as an essential part of setting L I a~ dual trace scope. Many dual trace oscilloscopes provide the option of displaying a single trace which represcants the sum of the voltages applied to the Y 1 and Y 2 inputs. In addition, it is possible t o invert one of the traces, say Y 2 , so that posi~ivc-going inputs deflect the trace downwards and negative inputs upwards. It is thus possible to

using oscilloscopes 69 display Y1 - Y2, i.e. the difference b e t w e e n the two input signals, instead of the sum. This will result in no deflection of the trace if the same signal is applied to both Y inputs - provided they are set to the same volts/div setting (and both variable controls, if provided, are at the calibrated position). Thus the oscilloscope will only respond to the difference b e t w e e n the two inputs, just w h a t is w a n t e d for e x a m i n i n g two wire signals that are balanced about ground. This property of ignoring or rejecting identical signal components at the two inputs is called ' c o m m o n m o d e rejection' or 'input balance'. The u n w a n t e d ' p u s h - p u s h ' or c o m m o n m o d e c o m p o n e n t that is rejected is referred to as ' c o m m o n m o d e noise', 'longitudinal noise' or 'noise to ground', whilst the p u s h pull signal is called the 'transverse', 'metallic' or ' n o r m a l m o d e ' signal. Two-wire balanced transmission systems are widely used, e.g. for transducer signals in factory process control systems, as twisted pairs in multi-pair telephone cables and for the t w o - w i r e overhead subscriber's loop connecting the domestic telephone to the nearest telegraph pole. The Y1 - Y2 m o d e will typically provide a 2 6 d B CMRR ( c o m m o n m o d e rejection ratio), m e a n i n g that the sensitivity to undesired c o m m o n m o d e signals, e.g. 50 Hz mains h u m , is only o n e - t w e n t i e t h of the sensitivity to the w a n t e d transverse signal. This is only a modest degree of input balance c o m p a r e d w i t h special scopes and other i n s t r u m e n t s specifically designed for working on balanced systems. However, balanced systems are generally used only up to a few h u n d r e d kilohertz at most, and instruments specifically designed for such use are correspondingly limited in bandwidth. Note that if 10:1 passive divider probes are in use, the 20:1 CMRR m a y be degraded, owing to within-tolerance differences in the exact division ratios of the two probes. With or w i t h o u t probes, the CMRR can be optimized by connecting both inputs to the same signal source and adjusting one or other Y channel variable gain control to trim d o w n the gain of one channel to exactly m a t c h that of the other. With care, up to 100:1 CMRR (40 dB balance) or m o r e can be obtained for signals up to a few h u n d r e d kilohertz, but this will not usually be m a i n t a i n e d over the full b a n d w i d t h of the scope. To m a i n t a i n this

70 Oscilloscopes increased CMRR, r e a d j u s t m e n t will also be necessary if the two Y i n p u t volts/div switches are set to a n o t h e r ( c o m m o n ) setting. W h e n using an oscilloscope's Y1 - Y 2 m o d e for balanced m e a s u r e m e n t s , b e w a r e of a potentially severe limitation. If the u n w a n t e d c o m m o n m o d e signal (e.g. mains h u m ) is m u c h larger t h a n the desired signal, it can overload the Y input amplifiers, resulting in a distorted and inaccurate display. This p r o b l e m can be avoided by using a p u r p o s e - d e s i g n e d differential probe. In the Tektronix P6046 Differential Probe and Amplifier Unit, the differential signal processing takes place in the probe itself, the amplifier producing a single-ended (unbalanced) 5 0 ~ o u p u t suitable for connection to any oscilloscope's Y input channel. The P6046 provides 10 000:1 CMRR at 50 kHz and no less t h a n 1000:1 even at 50 MHz, while c o m m o n m o d e signals up to +5 V peak to peak (+50V with the clip-on x l 0 attenuator) can be handled w i t h o u t overload, even w h e n e x a m i n i n g millivolt level signals. In p o w e r engineering it is often necessary to e x a m i n e small signals in the presence of very large c o m m o n m o d e voltages, for e x a m p l e w h e n checking that a silicon controlled rectifier's gate to cathode voltage excursion is within permitted ratings, in a m o t o r control or inverter circuit. The Tektronix A6902B Voltage Isolator uses a c o m b i n a t i o n of transformer- and opto-coupling to provide up to +3000 V (d.c. + peak a.c.) isolation from g r o u n d for each of two input channels. Designed for use with any t w o - c h a n n e l oscilloscope, the A6902B permits simultaneous observation of signals at two different points in the same circuit, or signals in two different circuits w i t h o u t respect to c o m m o n lead voltages. The t w o channels can also be combined to function as an input to a differential amplifier, for floating differential m e a s u r e m e n t s .

Use of Lissajous figures It might seem that n o w a d a y s the use of Lissajous figures for comparing frequencies is 'straight out of the A r k ' - w h y not simply use a frequency counter? But in fact there are several cases w h e r e the use of a Lissajous figure can provide m o r e information, and provide it faster. Suppose, for example, one had a precision 1 MHz frequency standard consisting of an oscillator controlled by an o v e n e d

Using oscilloscopes

71

(i) frequency ratio 3:1 (Y:X)

(ii) frequency ratio 3:2

(iii)-frequency ratio 3:2 (but with different phasing)

(a)

(b) Figure 5.6 (a) Lissajous figures (courtesy AEG Telefunken). (b) Frequency m e a s u r e m e n t with Lissajous patterns requires a k n o w n frequency sine wave on one channel, usually the X channel. If the u n k n o w n frequency has the exact ratio to the k n o w n frequency as shown above, then (depending on the phasing) the trace will be like one of those shown. Other ratios, e.g. 2:3, 3:4, etc., will give stable, though more complicated, patterns. In principle, any rational n u m b e r (i.e. m:n where m and n are integers) will give a stable pattern (courtesy Tektronix UK Ltd)

72 Oscilloscopes crystal. One could check its f r e q u e n c y w i t h a digital frequency m e t e r if the latter's internal reference w e r e accurate enough, or could be i n d e p e n d e n t l y checked. In the UK (and over m u c h of Europe), o n e could check by counting the carrier f r e q u e n c y of the BBC's Droitwich transmitter, w h o s e carrier is m a i n t a i n e d to an accuracy of one part in 10 ~. In fact, 'off-air frequency standards' are available commercially; these receive the Droitwich transmission, strip off the a m p l i t u d e m o d u l a t i o n a n d supply a 1 MHz o u t p u t locked to the carrier. However, even a 10 second gate time will only allow a 1 MHz f r e q u e n c y to be checked to an accuracy of +1 c o u n t in 107, w h i c h m a k e s checking the f r e q u e n c y m e t e r and adjusting the 1 MHz crystal oscillator a tedious business. Even then, the accuracy achieved will fall far short of that available from the Droitwich carrier. Suppose n o w that a Droitwich-derived 1 MHz sine wave and the crystal oscillator u n d e r test are displayed as a Lissajous figure; the effect of adjusting the crystal oscillator can be observed i m m e d i a t e l y and continuously. A f r e q u e n c y difference of as little as o n e - h u n d r e d t h of a hertz can be noticed in an observation time of a second or so, as the figure slowly drifts t h r o u g h the line-ellipse-circle repertoire of patterns. A counter w o u l d still have an u n c e r t a i n t y of plus or m i n u s o n e - h u n d r e d t h of a hertz or more, even after an observation time of 100 seconds. The Lissajous figure can also provide i n f o r m a t i o n about the stability a n d spectral purity of an oscillator. For example, if two i n d e p e n d e n t c o n v e n t i o n a l r.f. signal g e n e r a t o r s are both set to 100 kHz the resulting Lissajous display should be stable, giving a clean line and a r o u n d circle as the inevitable small frequency difference causes the figure to cycle slowly t h r o u g h its series of patterns. If n o w a Wien bridge type of RC oscillator is substituted for o n e of the signal generators, the poorer frequency and phase stability of this type of oscillator will be i m m e d i a t e l y apparent. The circle, instead of being perfeclly round, m a y s h o w m i n o r dents and the figure will wobble, rather like a jelly being carried on a plate. This is evidence of very l o w - f r e q u e n c y noise FM sidebands, w h i c h it w o u l d be difficult to resolve with even the most sophisticated s p e c t r u m analyser.


Z axis input A useful feature of m a n y oscilloscopes is a 'Z axis' input. In Cartesian coordinates the Z axis is the third dimension at right angles to the X and Y axes, and therefore the same as the direction of the electron b e a m w h e n the spot is at the centre of the screen. With no connection made to the Z axis input, the oscilloscope works normally with the trace brightness controlled by the intensity control, also affected by the timebase speed and sweep repetition rate as explained earlier. Applying a varying voltage to the Z axis input alters the brightness of the trace in sympathy. Some oscilloscopes have d.c. coupling of the Z axis input, but a.c. coupling is m u c h cheaper and therefore more common, whilst positive-going voltages result in a decrease of brightness if, as is c o m m o n l y the case, the Z axis input is coupled to the cathode of the c.r.t. The facility is useful in a variety of ways, one interesting example being the display of 'eye diagrams'. These are a way of examining the degradation due to imperfections of the m o d e m s and noise accompanying the signal at the receiver, in a digital phase-modulation communications l i n k Figure 5.7. The receiver for such a system will have a clock timing recovery circuit; displaying the i.f. (intermediate frequency) w a v e f o r m at the receiver with the scope triggered from this will not produce a coherent or useful picture. Bandwidth is a scarce and hence expensive commodity, and the sudden changes of phase s h o w n in Figure 5.8(b) imply the presence of wide signal sidebands. The modulated carrier at the transmitter is therefore first processed to produce a smoothly changing phase (by filtering and limiting, or other means) before being t r a n s m i t t e d - Figure 5.8(c). This illustrates 'BPSK' (binary phase shift keying) where there are just two possible transmitted phases. 'QPSK' (quadrature phase shift keying) systems have four possible phases at each clock or data stable time, permitting the transmission of two bi.ts of information per clock cycle or 'symbol'. To display an eye diagram, the recovered clock or symbol timing is used to generate a n a r r o w pulse occurring at the clock edge or data-stable time. This is applied to the Z axis input to

74

Oscilloscopes

bright-up the oscilloscope trace. The timebase runs repetitively, triggered from the receiver's carrier recovery circuit, or possibly in a bench test set-up, derived from the transmitter carrier as s h o w n in Figure 5.7. As the trace is invisible except during the bright-up pulse, i.e. at the sampling instant of the receiving

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Using oscilloscopes

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m o d e m , the phase of the received signal will be (ideally) in one of two possible positions 180 ~ apart, as indicated in Figure 5.9 (a), or in one of four possible positions in the case of QPSK. The resultant picture is called an eye diagram. In Figure 5.9 the open eye, such as should be obtained w i t h a well-set-up system, indicates little distortion; the nearly closed eye shows a system with excessive 'intersymbol interference' due to poor m o d e m design. Figure 5.9(b) alternatively gives an impression of w h a t one might see 'for real' over a digital radio link w i t h a very low received signal strength, the poor signal to noise ratio resulting in a nearly closed eye, and in consequence a high 'BER' (bit error rate) in the received data.

76 Oscilloscopes With the DSP (digital signal processing) capability built into m o d e r n DSOs, it is possible to derive m o r e i n f o r m a t i o n t h a n ever f r o m an eye diagram. Figure 5.10(a) shows (diagrammatically) a DSO acquiring points on a 'clean' eye diagram; with a poorer signal t h e r e w o u l d be m o r e r a n d o m n e s s to the point positions. Figure 5.10(b) shows h o w with a 'bit m a p p e d ' display w i t h I6 bits per 'pixel', the i n s t r u m e n t can, over a period, totalize the n u m b e r of sampled points falling in each pixel. The resultant eye

Figure 5.9 (a) Two-level digital phase-modulated signal showing well-set-up system with n~, intersymbol interference. (b) Poor system with bad intersymbol interference

Using oscilloscopes

77

diagram can be displayed in colour, with, say, single or low count pixels s h o w n in shades of blue, t h r o u g h the s p e c t r u m to red for the pixels with the highest counts. Additionally, the data can be further processed to show histograms illustrating the 'openness' of the eye in various ways, Figure 5.10(c). The oscilloscope in servicing Several of the facilities of a good scope have been discussed above in connection w i t h specific applications. The rest of this chapter looks at other particular areas of use for a scope. First, TV servicing is considered briefly; for a m o r e extensive t r e a t m e n t of the topic reference should be m a d e to one of the m a n y excellent books available dealing specifically with this subject. It is i m p o r t a n t to pay due regard to safety w h e n working on any type of mains operated e q u i p m e n t . This is doubly true w h e n working on TV sets, as some of t h e m do not have the circuitry and chassis isolated from the mains. The circuitry of the ubiquitous 12 in black and white portable set is designed to r u n from 12 V d.c. in order to permit operation from a car battery w h e n required. For mains operation a s t e p - d o w n transformer, rectifier and smoothing supply the required 12 V d.c. Thus only the transformer p r i m a r y is at mains potential, the rest of the set being isolated. Larger m a i n s - o n l y colour TV sets m a y have a type of switchmode p o w e r supply providing full mains isolation, but this is by no m e a n s invariably so. To avoid drawing a d.c. c o m p o n e n t from the a.c. mains (which was quite n o r m a l in the days of valved TV sets), non-isolated sets use a fullwave rectifier: as a result the set's circuitry and chassis can be at approximately half the mains voltage. The only safe w a y to proceed w h e n working on a TV chassis is to r u n it from a mains isolating transformer of a suitable rating. A 500 VA transformer should be more t h a n adequate. The television set's chassis should be firmly earthed, as is the case of the oscilloscope. Even then, one must be very w a r y of the high voltages present in the line deflection and e.h.t, sections of the receiver. No one should w o r k on a TV set w i t h o u t a d e q u a t e knowledge and expertise. Even apart from the safety aspect, m a n y faults will prove difficult or impossible to rectify w i t h o u t the full servicing

78

Oscilloscopes

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Using oscilloscopes

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79

Measurements on eye diagrams, see text (courtesy Tektronix UK

data for the particular model. Occasional loss of colour, for example, can be due to a variety of causes, and adjusting the controls in the w r o n g sequence can easily give you p e r m a n e n t loss of colour! The most convenient type of scope for TV servicing has built-in line and frame sync separator circuits, e.g. the Fluke model 3094

80

Oscilloscopes

featured. i.n Chapcer 3 . These are handy when examining t.h.e operation of line and frame dellrt:iion circuits respectively, particularly when the set is receiving live programme material. The TV sync circuits enable the scope to be triggered stably from the output ol the video detector. However, it should be possible to trigger an y good oscilloscopc from thc linc sync component of the video waveform by selecting normal trigger, positive or negative slope as required, and adjusting the level control to trigger o n the tips of the video, i.e. the sync pulses. Problems may be encountered in the case of a cheaper black and white set (with mean level AGC applied to the vision i.f.) on programme material, as the sync level will change with scene changes, the video being a.c. coupled. This problem is easily solved by using instead the signal from a greyscale or colour bar generator. Servicing hi-fi equipment is a less complex task than servicing a TV set. A low-distortion sine wave a.f. signal generator and a scope should enable sufficient testing for all practical purposes to be carried o u t . D u m m y load resistors, of a suitable rating, to replace the loudspeakers during full powcr testing can be described as a necessiiy rathcr than a luxury. A sine wave t.est. signal can bc followed through the various stages a n d a n y gross distortion observrd and pinpointed 10 the offending stage. In addition to clipping the signal on posi~ive or negative peaks (usually a sign of a f a u l t y bias network), a widehand scope may reveal that the amplifier brcomcs unstable with bursts of oscillation on one o r both peaks of the waveform at full drive, while behaving normally at lower Ievels. On live programme material, this can give rise to a nasty tearing noise appearing in loud passages only. Quite apart from these extreme forms of distortion, an amplifier (or m u c h Iess often a preamplifier) may exhibit 1 or 2 per cent distortion, usually more noticeable at higher volume levels. It is very difficult t o detect even several per cent of third harmonic distortion simply by examining the output waveform on a scope, birr the diagnosis is much easier if it i s possible t o display the undistorted test sine wave input on the other trace of the scope for ct)mparism. Unlike third harmonic (and other higher odd-ordcr) distorticin c ~ j r r ~ p o n e ~second ~ t s , and other cvcn-ordcr harrnonic disrortion affect. the positive and


negative half-cycles of the w a v e f o r m differently, usually m a k i n g one flatter and the other more peaky. Consequently, with care even 1 per cent of second-order h a r m o n i c distortion can be seen by e x a m i n i n g the trace. Of course, even 1 per cent of distortion completely disqualifies any amplifier from a n y pretence to the title 'hi-fi', but it is surprising h o w m a n y of the less expensive amplifiers on the market, especially those forming part of a cheap packaged 'music centre', do little better t h a n this, particularly at the e x t r e m e bass and treble ends of the audio range at full p o w e r output. In m a n y hi-fi outfits, the p o w e r amplifier for each stereo channel h a s been condensed into a single p o w e r IC (integrated circuit); often indeed both channels are contained within a single IC. So here, it is simply a case of servicing ( w h e n needed) by replacement. Preamplifiers are m o r e likely to be a m e n a b l e to servicing, in that there will often be separate, identifiable s t a g e s for input equalization, tone controls, balance, etc. To m e a s u r e the distortion in a 'real' hi-fi amplifier a scope will not suffice. A total h a r m o n i c distortion (t.h.d.) m e t e r is required, to remove the original sine wave from a sample of the amplifier's output and m e a s u r e the relative amplitude of the residual signal. This consists of harmonics, noise and, very often, 100 Hz h u m from the mains p o w e r supply. M a n y t.h.d, meters m a k e the residual signal available for e x a m i n a t i o n on an oscilloscope, w h i c h can be very informative. For example, once the f u n d a m e n t a l is removed, it is very easy to see w h e t h e r second or third h a r m o n i c predominates, while the presence of little pips of alternate positive- a n d negative-going polarity indicates 'cross-over' distortion in a class B amplifier. Class B amplifiers are the n o r m nowadays, only the most expensive amplifiers working in class A. Often also, class B amplifiers show considerable 100 Hz ripple in the residual at full p o w e r output, due to p e n n y - p i n c h i n g in the size of the smoothing capacitors of the p o w e r supply. At low volume, the class B o u t p u t stage draws little current, so there is little ripple voltage appearing on the supply rails, while at full o u t p u t the designer relies on the loud p r o g a m m e content to mask the h u m . Provided it has sufficient b a n d w i d t h to cope with the signal, an oscilloscope can be very useful w h e n developing or troubleshooting radio frequency circuits. The m a i n point to w a t c h for

82

Uscilloscopcs

hcrc is t h e cffcct of the loading imposed on the r.f. circuit. Even using a good 10:1 dividcr prohc, the incru act of looking at a i l i-,f. circuit can d r t u n r it o r cause i t t o oscillatr. This has already been covered in Chapter 4,which contains suggestions for coping with the problem, so no niore will be said CHI that topic here. Bandwidth The bandwidth quoted for a n oscilloscope generally refers to the frequency at which the amplitude has fallen by 3 dB. Remember therefore that if examining a 25MHz sine wave with a scope having a quoted 25 MHz bandwidth. the trace will show only 71 per cent of the true amplitude of the signal. Furthermore, the waveform being observed may be ralher severely distorted if not a sine wave, since the harmonics have frequencies of 50 MHz, 7 5 MHz, etc., and the oscilloscope's response at these frequencies will be very low indeed. Even an ideal 25 MHz squarewave will l o o k tolerably like a sine wave on a 25 MHz scope! Actually, the situation is a little iiiorc cotiiplica~cd than this. 'k'he rated bandwidth of the highcst qiiality oscilloscopcs is quoted as that frrqiicncy 4 1 whicli the responsc ( t o a signal which, were it a lower lrtqiitwcy, woiild give t i i l l scrccn dcflcction) h a s fallcn by 3 d B . Other manut'acturcrs quote t l i c ' I)aridwidIIi as Ihe - 3 d R point for Iialf-screen-hciglit signals, perhaps not unreasonable for a dual trace scope. One North American manufacturer - whose products I havcn't seen advertised for wine time now - quoted the bandwidth at the - 6 d B (50 pcr cenl response) point for quarler-screen-height deflection. Lct 1hc buyer beware. The screen height (lull screen, hall' screen o r whatever) at which the bandwidt ti is quoted is important, as the amplifiers driving tlic Y plates arc nowadays o l t c n slew-rate limited; this is cxplained in more detail in Chapter 10. It means, however, that provided one contents oneself with corisidcrahly less than fullscreen dellection, the bandwidth of thc scope is often effectively grc'a1c.r t h a n t tic q i i o t d figiirv. Ilnt'oriiinately, as the input. l'requency rises, so does the amplitiidc rcquircd to operate the trigger cit-cuiti-y. Tliiis when trying t o obscrvc a signal that is beyond the lull-screen handwidth of tlic oscilloscope, tlic arriount of c x ~ r i handwidth ~ IO had b y rcducing the displayed b c b

Using oscilloscopes

83

Figure 5.11 With a m a x i m u m sampling rate of 40 Ms/s, the IEC 1010-I Cat. III safety-rated OX8032 features true differential inputs. With input sensitivity ranges from 10 mV/div to 200 V/div, floating and three-phase measurements can be made without the need for passive divider probes (reproduced by courtesy of Chauvin Arnoux UK Ltd)

amplitude is limited to the point at w h i c h the trigger circuit ceases to function. If one is simply trying to see w h e t h e r there is a signal of any sort there (for example, trying to find out w h e t h e r the local oscillator of a Band II f.m. receiver is working and on approximately the right frequency, using a 40 MHz scope), t h e n the Y input sensitivity can be increased, if n e e d be right up to m a x i m u m . No quantitative amplitude m e a s u r e m e n t will be possible of course, but as a qualitative indication of w h e t h e r the oscillator is functioning or not, useful information has b e e n obtained. Even if the trigger circuitry will not lock the picture, you can still see if there is any signal there or w h e t h e r the oscillator is dead. Just h o w far b e y o n d the maker's n o m i n a l b a n d w i d t h an oscilloscope can still provide useful information depends not only on the frequency at w h i c h the trigger circuitry gives up the ghost, but also on the design philosophy of the Y amplifier. If the designer was aiming at m a x i m u m bandwidth, the frequency response m a y have been propped up at the top end w i t h n u m e r o u s bits of compensation and peaking c i r c u i t s - this enables the m a n u f a c t u r e r ' s sales d e p a r t m e n t to quote an impres-

84 Oscilloscopes sive figure for t h e i n s t r u m e n t ' s b a n d w i d t h . In this case, at f r e q u e n c i e s b e y o n d t h e design m a x i m u m , t h e Y amplifier r e s p o n s e m a y fall a w a y rapidly. But t h e d e s i g n e r m a y h a v e b e e n a i m i n g i n s t e a d at a fast r i s e t i m e for pulse a n d s q u a r e w a v e signals, c o u p l e d w i t h n o r i n g i n g a n d only 1 or 2 per c e n t o v e r s h o o t w h e n displaying a n i n p u t signal w i t h a r i s e t i m e m u c h less t h a n t h a t of t h e oscilloscope. In this case, t h e fall-off of f r e q u e n c y r e s p o n s e b e y o n d the n o m i n a l b a n d w i d t h will be m u c h m o r e gradual. W i t h t h e e v e r - i n c r e a s i n g i m p o r t a n c e of digital circuitry, n e a r l y all m o d e r n scopes will exhibit this m o r e desirable f o r m of h i g h - f r e q u e n c y r e s p o n s e . The result is t h a t a scope w i t h a 20MHz-3dB full-screen b a n d w i d t h m a y be able (given sensitive e n o u g h trigger circuitry) to display a 4 0 M H z squarew a v e at o n e or t w o divisions vertical deflection. Of course it will n o t a p p e a r q u i t e like a s q u a r e w a v e , but on t h e o t h e r h a n d t h e f l a t t e n i n g of the p e a k s will m a k e it clear t h a t it is n o t a sine w a v e . The oscilloscope is doing its best to tell you t h a t the w a v e f o r m is s q u a r e . Thus, used w i t h intelligence a n d u n d e r -

Figure 5.12 Tile two channel HM2005 real-time analogue oscilloscope features a 200MHz bandwidth, limebase speeds tt~ 2ns/divisit~n (with • magnifier on) and separate lrigger controls for lhe A and I3 timebases. Cursor functions provide alphanumeric readout of w~ltage, time and frequency measurements; an RS232 interface and component tester (see Figure 5.13) are built in (courtesy Hameg Lid)

Using oscilloscopes 85 standing, a n oscilloscope can p r o v i d e c o n s i d e r a b l e u s e f u l inform a t i o n , e v e n if o n l y of a q u a l i t a t i v e n a t u r e , w h e n

handling

signals well b e y o n d its n o m i n a l capabilities.

Component testing T h e r e is a n o t h e r m u n d a n e

b u t u s e f u l c h o r e for w h i c h

any

oscilloscope can readily be p r e s s e d i n t o service, be it a m o d e r n h i g h - p e r f o r m a n c e t y p e s u c h as t h a t i l l u s t r a t e d in Figure 3.1 or t h e m o s t m o d e s t of l o w - p r i c e d c o m m o d i t y scopes. F i g u r e 5.13 s h o w s h o w a l o w - v o l t a g e w i n d i n g o n a m a i n s t r a n s f o r m e r plus a resistor can be w i r e d for use as a c o m p o n e n t c o m p a r a t o r . W i t h t h e circuit s h o w n , resistors f r o m less t h a n 100 f~ to o v e r 10 k ~ can be c o m p a r e d -

for h i g h e r or l o w e r v a l u e s t h e line b e c o m e s

too n e a r l y h o r i z o n t a l or vertical to p r o v i d e m u c h u s e f u l discrimi n a t i o n . Similarly, capacitors a n d i n d u c t o r s can be c o m p a r e d o n a g o o d / b a d basis, o v e r a b o u t a 100:1 r a n g e of values.

_ vertical (Y) 3.3 K input 1/2 w out-of-circuit

'IF

330 r7 1/2 w l l I

I

in-circuit 120 ~'~ ~6.3 VAC~-~ ','. ~1 ~ VAC

=-scope ground

1 i

short

,1i

= horizontal (X) input

test probes open

waveforms capacitance diode ,

resistance

Figure 5.13 X-Y component checking requires the transformer circuit shown above. With it connected to your scope and the scope in the X-Y mode, patterns like those illustrated indicate the condition of the component. The patterns shown can be seen when the components are tested out of the circuit; in-circuit component patterns may differ because of the resistors, capacitors and other devices connected to the component under test (courtesy Tektronix Inc.)

86

Oscilloscopes

Figure 5.14 With its 100Ms/s 8 bit samples and 100MHz bandwidth, the Metrix OX8100 provides sensitivities down to 2 mV/division on both input channels, and sweep speeds down to 50ns/div (reproduced by courtesy of Chauvin Arnoux UK Ltd)

Figure 5.15 Economical, both on price and bench space, the 100MHz bandwidth TDS224 features 1GS/s sample rate on all four input channels. With a nlaximum sensitivity of 2 mV/div., the TDS224 offers display options including s i n x l x interpolation, dot or vector dot-joining, persistence of 1, 2 or 5 seconds, or infinite, or OFF (courtesy Tektronix UK Lid)

Using oscilloscopes 87 Some m o d e r n mains-operated scopes use a direct off-line switching p o w e r supply. In addition to cost and weight reduction, this a r r a n g e m e n t has other advantages. The supply can act as a preregulator for the stabilizers used by the various voltage rails, and can in addition cope with any mains input voltage from 90 V to 260V w i t h o u t any mains voltage adjustment selector. However, m a n y mains-operated scopes use a conventional mains transformer, so that one of the items required in Figure 5.13 is already available - it just needs a n o t h e r low voltage, low current, secondary winding. Thus for very little extra cost, a c o m p o n e n t test facility can be incorporated, although usually a single fixed value of resistor is used, resulting in a rather restricted range of values for w h i c h good discrimination can be obtained. Nevertheless, the a r r a n g e m e n t is very popular and useful and is consequently found in a n u m b e r of low-cost instruments.

6

Sampling oscilloscopes In addition to the ART (analogue real-time) oscilloscopes at which this book has looked so far, there are other types of great importance; in particular sampling oscilloscopes and D S O s digital storage oscilloscopes. The latter have gained wide acceptance as the limitations of the early models have been overcome, n e w techniques to extend their capabilities being introduced with almost bewildering speed. Chapter 7, then, is devoted entirely to DSOs. But we will look first, in the rest of this chapter, at sampling oscilloscopes. There are four reasons for doing things in this order. First, historically speaking, sampling oscilloscopes predate DSOs by the best part of two decades. Second, an important class of DSO - the digital sampling oscilloscope - uses exactly the same technique for capturing a repetitive, very high frequency waveform as that used in the traditional sampling oscilloscope described in the r e m a i n d e r of this chapter. This technique is thus of extreme c o n t e m p o r a r y importance, even though the type of sampling oscilloscope described below is no longer in current manufacture. Third, it will enable us to clear up one p h e n o m e n o n - aliasing before tackling the increasingly complex digital storage scene. And fourth, although they no longer feature in oscilloscope manufacturers' catalogues, there are of course m a n y analogue sampling scopes, as distinct from the later digital sampling oscilloscopes, still in use. Both sampling scopes and DSOs look at an input signal at discrete 'sampling' instants, rather than continuously like an analogue real-time scope. They are therefore only aware of the state of the signal at these instants and are completely ignorant of what happens in b e t w e e n the samples. This ignorance is the basic cause of aliasing, as will become apparent shortly. Analogue sampling oscilloscopes, which I shall call simply sampling oscilloscopes from here on, offer certain advantages over ordinary real-time scopes but, as is always the case in -

Sampling oscilloscopes 89 electronics (as indeed in life itself), these advantages are not obtained w i t h o u t some accompanying limitations. Sampling scopes were introduced in the late 1950s and offered u n h e a r d - o f bandwidth compared with real-time oscilloscopes of the day. In the latter, by using a 'distributed amplifier' consisting of m a n y valves effectively harnessed in parallel, and restricting the c.r.t.'s Y deflection range to just four divisions against the eight provided as standard nowadays, a b a n d w i d t h of 85 MHz was achieved. In contrast, the Hewlett-Packard model 180 sampling oscilloscope boasted a b a n d w i d t h of no less t h a n 2 GHz (2000MHz), more t h a n twenty times that of the best real-time scopes of the day. Subsequently, following great advances in the design of cathode ray tubes and using advanced solid state circuit techniques, real-time oscilloscopes with a b a n d w i d t h of 500MHz became available from a small n u m b e r of manufacturers. The state of the art was represented by the n o w discontinued Tektronix 7104 oscilloscope, with a b a n d w i d t h (via the u amplifiers) of 1000MHz, or in excess of 2 0 0 0 M H z for signals connected directly to the Y plates of the cathode ray tube. Corresponding advances in sampling oscilloscopes led to instruments w i t h bandwidths of 14 GHz in the early 1970s, and latterly to the Tektronix l1801B DSO. This digital sampling oscilloscope (as distinct from an ordinary digital storage oscilloscope) has p u s h e d the b a n d w i d t h of such instruments of 50 GHz. Thus there is m u c h the same ratio b e t w e e n the m a x i m u m bandwidths of real-time and sampling oscilloscopes as prevailed in the 1950s. So h o w do sampling scopes achieve their notably superior bandwidth? And w h a t are the limitations which were m e n t i o n e d earlier? Clues can be gained from the block diagram of a basic real-time scope, see Figure 2.1. The b a n d w i d t h limiting factors there are the input attenuator, Y amplifier, Y deflection stage and of course the c.r.t, itself. The techniques used to maximize the b a n d w i d t h of the attenuator and amplifiers are discussed in Chapter 10 whilst the corresponding techniques in the case of the c.r.t, are covered in Chapter 9. The sampling oscilloscope avoids all these limitations at one fell swoop, by simply not attempting to deal with the whole signal in real time. Instead, it takes samples

90 Oscilloscopes

of the instantaneous voltage of t he input signal o n succcssivc cyclcs and asscmhlcs these samples to forrrl a pict.ure OI the comp1er.e wavdorrn. It can m l y operate in this way if the signal goes on repeating from cycle to cycle for as lorig as it takes lo build up the display. Herice the sampling oscilloscope is limited to displaying repetitive wavcforrns. This is one limitation. Another results from the omission of input attenuator and input amplifier. The size of the largest input signal which a sampling oscilloscope can handle is quite restricted, only a few volts peak to peak including any d.c. component. Fortunately, when using a sampling scope w e are often interested only in the a.c. behaviour of the circuit under investigation. So a.c. coupling can be used to prevent any d.c. level present eating away at the usable a.c. input voltage range, whilst for handling larger signals, a x l 0 attenuator can be used. Likewise, the omission of a n input amplifier limits the usable range in the other direction, the smallest signal swing viewable being limited by sainpling noise - the irlevitable small sample-to-sarnple voltage variations which occur even when the input voltage itself is not varying. T h u s rhe main requirt?ment for ;I sampling oscilloscope is a circuit capable of accurately sampling t h e iriput wavelorrn a l i-rgular inlrrvals. I n a riulshell, this is the strohoscopic technique used to slow down the motion (or I'requericy) of everits which are too fast l o observe by conventional means. If we want to study some mechanical cvcnt like the turning of gears which rotate too fast for the eye t o see, we can illuminate them with a stroboscope. If they are repeatedly briefly lit once per revolution, or once after several complete revolutions, they will present a stationary image. But if after each revolution (or group of revolutions) we light them u p a small amount of time later (say At later), then the eye sees samples a t successively later positions, a n d if this happens continuously, the eye can be deceived into seeing continuous (albeit much slowed down) mor.ion - rhe same effect wrhich in a movie rnakes the spokes of a wheel sccm t o bc tiirriirig slowly o r even turning backwards whcn the vehicle is in fact travelling forwards rapidly. This is a direct analogy o f 'sequential sarnpling', the most co ni in on r rch n i q 11e 11siid i n sa m p I in g scopes.

Sampling oscilloscopes 91 signal trigger real time

samples taken

~ At

~!

$I',

~" ,

~ I

,

,

$

I

'

, ,

~

I ~

',

" ~

, ,

'~

',~

$

:

I

:

!'_'"",,"A=L'I,'"I .... ' l,,,,I ....~ I,,,,I ....'!,,,,I .... '1.... i .... I .... 1.... J,',,,I .... I,,I,! .... I,,,i1,,,,I,,,,1 0 5 10 15 20 25 30 35 40 45 50 55 60 65 70 75 80 85 90 95 1 0 0 1 0 5 1 1 0 ns

e- _--t-

-9- - - ' e ' - - - e ' - - oscilloscope

- --o- ....

~ -- -'e-

---e-

--"~----e

display

[ -;- 19

equivalent time

1.... 1.... 0 5 10 ns

Figure 6.i When viewing a low frequency, a sampling oscilloscope may take one sample per cycle of the input waveform, as here

Figure 6.1 illustrates the basic process. A signal is applied to the vertical input of the sampling oscilloscope, and also (internally or externally) to its trigger circuitry. Assume that the negative tip of the w a v e f o r m just causes triggering, and that the first sample of the signal voltage is t a k e n at that instant. On the oscilloscope a dot appears in the correct vertical position. On the next signal cycle a trigger pulse again occurs at the same point on the waveform, but this time circuitry in the scope delays the taking of the sample by the time i n c r e m e n t At. This second dot will appear at an appropriately higher level on the c.r.t., and it m u s t also be displaced to the right by a distance representing the time delay At. Subsequent samples build up a dot representation of the complete waveform. Figure 6.2 shows the same procedure, except that instead of taking a sample from every cycle of the input waveform, here a sample is only t a k e n from every nth sample. So now, the timescale on the oscilloscope screen does not represent, as in ordinary real-time scopes, the actual or real time at w h i c h the sample was t a k e n (a little over 11 ns after the first sample), but represents instead the time equivalent to the distance b e t w e e n the two samples, had they b e e n on one and the same signal cycle (0.2 ns). The user of a sampling oscilloscope will not usually be

92

Oscilloscopes

aware of, nor w a n t to know, h o w m u c h real time elapses b e t w e e n samples; he or she is only concerned with the timescale of the reconstructed image. In practice, the sampling rate is seldom as high as Figures 6.1 and 6.2 might suggest. Typically, the sampling rate is a r o u n d 100 ks/s (kilosamples per second). So the 500 MHz triangular wave s h o w n in Figure 6.2 would in fact be sampled on every 5000th cycle. To briefly recapitulate. The c.r.t, display is built up of discrete dots whose vertical positions correspond to the signal voltage at the time of sampling and whose horizontal positions correspond to the time delay between the beginning of the next sampled waveshape and the m o m e n t w h e n the sample is taken. To recognize the beginning of the waveshape, the instrument uses trigger circuitry m u c h like that of a conventional oscilloscope. The trigger circuitry will be preceded by a divider stage and gating, to limit the sampling rate to 100ks/s or so. High speed logic circuits such as ECL (emitter coupled logic) can cope up to 1 GHz or higher. For triggering from very high-frequency signals, e.g. from several GHz upwards, the design may employ a tunnel diode or similar specialized circuitry, providing 'trigger countdown'.

signal

!

~

~

0.2 ,--~i4 n s l

,o

,I

trigger ~At real

time

~t

'

,,

~I

l

~t

i~a ~J~ ~I

I

I

',

I'

'

i

~l ....

'

I m " " " ~ " ' l J " l J l ' " J l l " ' l ' l " l ' l ' l i J .... 1.... l~,,,lh,,,l,,,,l,,,jll~,l,l,,,,l,u,,,l .... l,,i,l,,,,l, 0 5 10 15 20 25 30 35 40 45 50 55 60 65 70 75 80 85 90 95 100105110ns

samples taken

~

_~__-o~--4---~

e .

oscilloscope

equivalent

.

- _ _._ .

4---~---

~

---i

-----'~

display

[ ";'" 1 lee

time

.

o%

0 1 2 ns

Figure 6.2 A sampling oscilloscope may take one sample per cycle of the input as in Figure 6.1, or, more typically, one sample per n cycles of the input, as here. In this example n = 5, but in practice n could equal, say, 50, 500, 5000 or any larger n u m b e r

Sampling oscilloscopes

93

s,0o , trigger At real 0.2 n

~ ~

~

~

$

time 0 5 10 15 20 25 30 35 40 45 50 5560 65 7075 80 85 90 95100105110ns samples taken

_,r=..=._ _-o--

o---~ ....

0"

"

4='-- -- -. 0........4l

oscilloscope display

equivalent time

i

I

1

0 1 2 ns

Figure 6.3 W h e r e the input is of a constant shape, but irregular occurrence, the sampling oscilloscope can still reconstruct the signal, as s h o w n

The ability of the i n s t r u m e n t to recognize a certain point on the waveform and trigger on it, and t h e n delay the taking of successive samples by increasing a m o u n t s of time, m e a n s that the sequential sampling oscilloscope can do something no stroboscope can do; it can successfully sample a repetitive but irregularly recurring waveform. This is illustrated in Figure 6.3. Note, however, that this capability is limited to sequential sampling mode. The r a n d o m sampling mode will not w o r k with irregularly spaced samples, for reasons which will appear later in this chapter. Note that if it is desired to examine the leading edge of an irregularly occurring fast pulse, a delay line must be used b e t w e e n the trigger take-off point and the sampling gate as indicated in Figure 6.4. The sequential s a m p l i n g oscilloscope The block and timing diagrams of a typical sequential sampling scope are as s h o w n in Figure 6.4. The signal is routed from the input socket to the trigger take-off circuit, w h e r e a few per cent of the signal energy is extracted for use in the internal trigger mode. Alternatively, an external trigger signal can be used, if available. Trigger and hold-off circuitry is comparable to that in

feedback E

signal r 7 r"---1 ~ , / . d,ff. ('~b,---i trigger L_~ delay i _ J sampling [ j J a . c .

'~ l take-~ qLli-ne-J-Lgat~e[ ,

e•

I

s,~obe I f

1

"I/

int. l . _ ~ m e m o r y ~

n')nl --'~']amPl'f'ir I lgati

I I

reset 4

(a) signal

i

1 ~ ~

i i

I

fast ramp 2 inverted staircase 3 on same scale sampling c o m m a n d 4 (b)

stairstep advance 4

tl

5 retrace blanking

interdot blanking 4

trigger

or strobe pulse staircase 5

display | ,amplifierJ

~te

f i [ trigger u~,u~, l_. J 3 /,1 5 [staircase ] trigger] 1 I fast 121 strobe ('~ " J - ~ ramp ~1 comparator J ' ~ ~ [ generatorJ

t

I

^ t

_I"display !

-I amplifier I {

11

=[ blankingl[ .j

I

,

I

--~ x + ~t

,,!

,, ~,

A

.....

Figure 6.4 (a) Block diagram. (b) When the fast ramp (originated by the trigger pulse) crosses the slow ramp or 'staircase' waveform, a trigger pulse is generated


95

any high-frequency oscilloscope, and if the trigger level and slope are correctly set, the trigger pulse, w a v e f o r m 1, can be made to occur very near the beginning of the waveshape of interest. The two blocks following the trigger circuit provide the variable delay. Each trigger starts a fast ramp, w a v e f o r m 2. This ramp and waveform 3 are fed to the strobe comparator, and w h e n the ramp has r u n d o w n to the initial level of w a v e f o r m 3 the comparator puts out a sampling pulse. This pulse operates the sampling gate which consists of a set of balanced diodes, often in a bridge configuration, which are made to conduct, and so permit the signal voltage present on the input side to appear at the output of the gate. No matter h o w low the source impedance of the signal is, and h o w high the input impedance of the sampling gate, some finite a m o u n t of energy will have to be drawn from the signal circuit during the gate conduction period to charge the capacitor at its output. To this extent, we are interfering with the signal, and at frequencies in the GHz region this interference will appear as a w a v e f o r m distortion k n o w n as 'kickout'. In order to minimize it, the capacitor at the output of the sampling gate is made extremely small, which means the voltage level transferred to it will disappear in a matter of n a n o - i f not picoseconds. But if we w a n t to see a bright display on the c.r.t., the b e a m should be held at the points corresponding to each sample until just before the circuit is ready to take the next sample. The level at the o u t p u t of the sampling gate is, therefore, after suitable amplification, gated into a m e m o r y which t h e n drives the vertical deflection plates via a conventional o u t p u t amplifier. (Details of the feedback loop s h o w n in Figure 6.4 will follow later in this section.) Since the fastest sampling rate used in a typical sampling oscilloscope is, say, 100 kHz, the signal coming from the sampling gate cannot possibly change any faster t h a n once every 10 p,s. All the oscilloscope circuits following the sampling gate can therefore be designed in the most modest way. This is the whole point of sampling. We cannot design real-time oscilloscopes capable of looking at signals of m a n y GHz, or risetimes of a few picoseconds. But we can, if the signal is repetitive, sample it and handle the sample gate output with circuits designed for no more than, say,

96 Oscilloscopes 1 MHz. (By c o m p a r i n g Figure 6.4 w i t h Figure 2.1, you can see that we have disposed of all the b a n d w i d t h - l i m i t i n g items in the Y signal chain. The limiting factor n o w is h o w short a sample of the signal we can take - if a w h e e l is t u r n i n g so fast that each single flash of the stroboscope illuminates one complete revolution, we n e e d shorter flashes.) W a v e f o r m s 2 a n d 3 in Figure 6.4 have resulted in a sample being t a k e n as s h o w n , at a particular point on the signal. The circuit m u s t n o w readjust itself so that after the n e x t trigger the sample is t a k e n later (relative to the signal cycle) by an a m o u n t At. To do this, the level of w a v e f o r m 3 is adjusted as shown, a n d this can in fact be initiated by the strobe pulse. The succession of d.c. levels builds up to a w a v e f o r m k n o w n as the staircase, a n d since each step of this staircase corresponds to a time i n c r e m e n t At, and we wish to m o v e the c.r.t, b e a m horizontally by a m o u n t s corresponding to these same time increments, the staircase w a v e f o r m can also be used to drive the horizontal deflection circuit. The fact that in Figure 6.4 the staircase 5 is a positivegoing w a v e f o r m and the strobe c o m p a r a t o r requires a negativegoing w a v e f o r m is of no deep significance. We could have chosen a positive-going fast r a m p for 2 and t h e n 3 could be replaced by 5, saving the inverter. It has b e e n s h o w n as in Figure 6.4 simply because that is the w a y the majority of actual sampling scopes work. Note that the staircase w a v e f o r m could be replaced by a r a m p generator. However, in this case we w o u l d be limited to sampling regularly recurring, jitter-free w a v e f o r m s as in Figure 6.2. By using a staircase, w h e r e the next step is initiated by the sampling c o m m a n d , we can sample an irregularly occurring pulse as in Figure 6.3, since the 'treads' of the steps need not all be the same width. However, this clearly only works if the shape of the signal pulse is constant. To the right of the detailed w a v e f o r m s , 2 and 5 have b e e n r e d r a w n to a compressed timescale to s h o w the complete sequence. With a sufficient n u m b e r of samples across the screen, the staircase will be m a d e up of so m a n y small steps that to the n a k e d eye it appears exactly like a c o n v e n t i o n a l sweep sawtooth, in the same w a y that in the sampling display itself the dots m e r g e to give the a p p e a r a n c e of a c o n t i n u o u s trace.

Sampling oscilloscopes 97 Blanking is used not only to prevent the appearance of the retrace or flyback, but also to cut off the c.r.t, while the b e a m moves from one discrete sample position to the next; this is k n o w n as 'interdot blanking'. Now to r e t u r n to the feedback loop in the vertical circuit, and the reason for including it. It was stated earlier that energy is d r a w n from the signal circuit to charge a small capacitor (typically just the wiring and stray capacitance) at the o u t p u t of the sampling gate. W h e n the gate stops conducting, the voltage to which the capacitor was charged will quickly leak away, but before this can h a p p e n we amplify it, and gate it into a m e m o r y circuit w h i c h will hold this level. W i t h o u t any further circuit complications, we could reset the m e m o r y shortly before the next sample is due to be taken and start the process all over again. Such open loop m e m o r i e s were used in some cheaper types of sampling scope. The advantage of introducing a feedback loop is twofold. First, the feedback can be used to hold the voltage of the capacitor at the output of the sampling gate at the level of the sample just taken, and t h e n if the signal, w h e n the n e x t sample is taken, happens to sit at the same voltage level, no energy n e e d be d r a w n from it: the gate o u t p u t circuitry is already at that level. This minimizes kickout. It might seem a surprising assumption that the signal level might be the same on successive samples, but if we take a sufficient n u m b e r of samples to create a reconstituted display w h e r e the individual dots merge into a continuous trace, this does in fact m e a n that the signal level voltage changes from sample to sample are very small. The second advantage of the feedback loop is that it is selfcorrecting, m a k i n g the drcuit performance nearly i n d e p e n d e n t of amplifier gain variations. Figure 6.5 illustrates h o w the loop works. The diagram shows the situation w h e r e the signal, w h e n it is first sampled, is 2 units high. But the sampling pulse is e x t r e m e l y n a r r o w (as short as 30 ps or less) for the reason indicated earlier, and does not give the capacitor time to charge to the full 2 units. In Figure 6.5 it is s h o w n as charging to only half a unit. This represents a 'sampling efficiency' of 25 per c e n t - actually an optimistic assumption.

98 Oscilloscopes

' )'/ - - - ~

k,

signal-

/l

\

sampling gate pulses

_,.__

~ - ~

s a m p l i n g gate o u t p u t w i t h feedback

| ----1

'

m e m o r y gate pulses memory output

.

i I I

I

l t

Figure 6.5 Showing how the a.c. amplifier compensates for the typically low efficiency of the sampling gate

(Typical values might even be as low as 2 per cent.) The a.c. amplifier is a slowly responding one with the aim of getting f r o m it an amplified and 'time stretched' version of the input. The m e m o r y gate pulses, a l t h o u g h initiated from the strobe comparator, are also m a d e c o m p a r a t i v e l y long (typically 300ns). The m e m o r y is acting as an integrator, and its o u t p u t is the c u m u l a t i v e result of successive inputs. This o u t p u t drives the c.r.t. display amplifier. It is also fed back to the input via a very slow time constant n e t w o r k w h e r e it will take nearly 10 p~s to raise the input capacitor of the a.c. amplifier to the level that the signal h a d w h e n the sample was taken. The slow time constant explains w h y the sampling system c a n n o t take samples faster t h a n at a 100 kHz rate. W h y use such a slow time constant? As can be seen, the feedback used is in fact positive feedback (in the same direction as the original signal), and if it arrived while the memory gate (not the sampling gate) was still conducting, the loop gain w o u l d exceed unity and the system w o u l d be unstable. The gradual raising of the voltage on the input capacitor to the correct level of 2 vertical units is of course also amplified by the


99

a.c. amplifier, which explains the second, longer, lower bulge in its output waveform. But as the m e m o r y gate is not conducting during this period, it is of no significance. It is w o r t h noting that the combination of a.c. amplifier (acting as a differentiator) and m e m o r y (acting as an integrator) ensures that the d.c. component of the signal will in fact be passed by the circuit. Figure 6.5 shows a second sample t h e n being taken, and since at this time the signal is at 3 vertical units and the sampling gate output already sits at 2 vertical units, the circuit sees a potential difference across the gate of only 1 unit. With a sampling efficiency of 25 per cent, the o u t p u t moves only a quarter of a unit before the sampling pulse ends, but w i t h the same circuit gains as before this results in just the right a m o u n t of change to bring the m e m o r y o u t p u t to the correct level. Looking n o w at the solid-line drawing of Figure 6.6, the m o r e c o m m o n case is s h o w n where, at the time of the second sample, the signal is still at the same voltage as on the first. There is therefore no voltage across the sampling gate w h e n it conducts, no energy n e e d be transferred, no kickout occurs, the a.c. amplifier sees no change at its input and thus produces no output, and the m e m o r y remains at the same level. All is well in the best of all possible worlds. But Figure 6.6 also illustrates w i t h dashed lines h o w the feedback loop takes care of departures from this ideal. As an example, it has been assumed that the a.c. amplifier gain is excessive. This m e a n s that the m e m o r y o u t p u t will be too high, and the dot will appear too high on the c.r.t. Because, in Figure 6.6, the signal level for the second sample is unchanged, the action of the feedback loop can be seen very readily. W h e n this second sample is taken, the voltage at the gate output is in fact (erroneously) too high, so energy will be transferred in the opposite direction and the gate o u t p u t voltage will drop d o w n (by the usual 25 per cent of the difference). This negative change is seen and amplified and added to the m e m o r y , but since the a.c. amplifier gain is excessive, it will again result in too m u c h m o v e m e n t . The original overshoot is overcorrected, giving an u n d e r s h o o t of small amplitude. On the third sample the overshoot is reduced still further and on successive samples the

100 Oscilloscopes I

-

1

1

'

f.

J,,

1

!

X sig na I - -

, /t!

I

I

\

w,

I

------

; I

9

t

i sampling gate pulses

II

I

t--'----

~ ~ .sampling gate output with f e e d b a c k ~ I ij~ ac amplifier has e x c e s s i v e gain i I',! ~'~

~..._ . . . .

u

a c amplifier

I I

,!

kJ,~

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..

output

t ~

m e m o r y gate pulses

tv

/

'-\ I

I

;

I i].~

I -/f--r~emory output,

-~,

Figure 6.6 Effectively a time-discrete servo loop, the sampling system corrects for small loop gain errors, as shown

circuit settles to t h e correct level. If t h e s a m p l e s w e r e w i d e l y spaced a n d i n d i v i d u a l l y discernible t h e a p p e a r a n c e w o u l d be like that of a d a m p e d oscillation (see Figure 6.7(a)). Thus whilst in t h e short t e r m , i.e. on a s a m p l e - b y - s a m p l e basis, t h e feedback loop p r o v i d e s positive feedback, in t h e long r u n it d e m o n s t r a t e s t h e self-correcting, d i s t o r t i o n - r e d u c i n g effects of n e g a t i v e feedback. Exactly t h e s a m e effect w o u l d o c c u r if, i n s t e a d of excessive a.c. a m p l i f i e r gain, t h e m e m o r y circuit h a d too m u c h gain, t h e

9

(a) Figure 6.7

w

(I))

Sampling servo loop gain t()() high (a), ()r too low (b).


101

feedback path had less attenuation, or the sampling efficiency increased. All these conditions are covered by expressions like 'the sampling system has too m u c h loop gain'. If, conversely, the a.c. amplifier gain had been too low, the first sample would not have reached the correct level, and the difference between ideal and actual level would again have been seen by the circuit w h e n the subsequent samples were taken. In this case the result is a gradual approximation to the correct level, giving the appearance of simple undershoot (Figure 6.7(b)), a condition k n o w n as 'low loop gain'. This section has described how, in a traditional analogue sampling scope, positive feedback is used to boost the sampling gate output from just a few per cent to effectively 100 per cent, enabling the true signal amplitude to be measured at each sample. A similar scheme is used in digital sampling oscilloscopes, described in Chapter 8. In these, some manufacturers use an analogue feedback loop similar to that described here, whilst others use a feedback voltage derived from a DAC (digital-toanalogue converter) fed with a scaled version of the digitized sample just taken. A discussion of the relative merits of these two schemes, and of measures to deal with 'blow-by' (capacitively coupled breakthrough of the input signal whilst the sampling gate is not conducting and thus supposedly blocking the input), is beyond the scope (no p u n intended) of this book. Sequential sampling scope b e h a v i o u r It was mentioned in the last section that the results of incorrect loop gain, and the action of the feedback loop in such cases, was particularly well illustrated by Figures 6.6 and 6.7 because the signal level on subsequent samples was unchanged. Now on some instruments, a front panel control (usually labelled 'dot response') will allow the precise adjustment of the loop gain, and obviously the best kind of waveform to use during the adjustm e n t is one resembling Figure 6.7, such as a squarewave. Conditions of incorrect loop gain will be masked if the signal level changes from sample to sample, and in the most important special case of sine waves (whose shape is mathematically almost indestructible) low or high gain will simply result in a low or high

lO2 Oscilloscopes amplitude sine wave display (unless there were an unusually high 'dot density' or n u m b e r of samples per cycle of t h e waveform), which could totally mislead the u n w a r y user. A useful technique called 'smoothing', which is available on most sampling instruments, deliberately reduces the loop gain to a low figure, say one-third of normal. The result is that the first sample rises to only one-third of the final signal amplitude, and if the signal level remains unchanged, subsequent samples will each rise by one-third of the remaining difference, giving the usual exponential approach to the correct level. This is shown in Figure 6.8 (a). It can be seen that with a loop gain of one-third it takes twelve samples for the display to reach a value within 1 per cent of the final value. The rendition of a squarewave by such a series of dots appears intolerable, but if the dot density is n o w increased sufficiently (by reducing At to a really tiny increment), the twelve samples that fell short of the correct level can be made to b u n c h up so closely that the appearance of a squarewave is restored, as in Figure 6.8(b). So what has been gained? Since it takes twelve dots to reach the correct amplitude, only repetitive (signal) waveforms which are present during twelve successive samples will be displayed with full amplitude. Any r a n d o m variations, such as high-frequency noise, whose value varies from sample to sample, will be displayed with only one-third of [heir true

9 ~p =~ 9 "=,. ~.~ ~ v.o o>(?r ~

~ (a)

(b)

Figure 6.8 (a) Reduced sampling loop gain requires several samples to follow an input signal change. (b) But can still accurately delineate a fast edge, if the dot density is made high enough


103

amplitude. The smoothing technique reduces noise to a value corresponding to the reduction in loop gain; in the above example with a loop gain of one-third, the noise is reduced by 9}/2dB. The i m p o r t a n t point is that if the dot density is sufficient, this noise reduction can be achieved w i t h o u t affecting the shape of the signal - in other words, w i t h o u t reducing the b a n d w i d t h of the system. We have to pay a price, of course, and in this case the noise reduction is b o u g h t at the expense of time. With the great dot density n e e d e d in this mode, a flickering display or even a slow-moving spot m a y result. Nevertheless, it shows h o w a technique which is easy in the digital world was in the past achieved in the purely analogue sampling scope. In a m o d e r n digital sampling scope, the same effect could be achieved by acquiring the trace twelve times over and storing the average of the twelve samples for each given point as the result for that point. Here again, the noise reduction is b o u g h t at the cost of increased time. W h e t h e r you are observing a squarewave, a sine wave, or any other shape, it is i m p o r t a n t to m a k e sure that the dot density is sufficient to produce a true display. If a front panel dot density control (on some i n s t r u m e n t s labelled 'scan') is available, the simplest w a y to obtain this condition is to increase the density until no further change of amplitude or shape occurs. Insufficient dot density, even w i t h o u t smoothing, can sometimes lead to a 'false display'. One example of h o w this could occur is s h o w n in Figure 6.9. Looking first at the 1 MHz signal, with the At selected in the illustration five samples will be taken, one-fifth, two-fifths . . . . up the slope and the fifth sample at the top. W h e n displayed on the c.r.t, screen, these dots will give the appearance (quite correctly) of five points on a slope with a 2 5 0 n s risetime, and further samples (not s h o w n in the illustration) w o u l d complete the picture of a 1 MHz trapezoidal waveform. Thus a true display of the 1 MHz signal is built up on the screen. But looking at the lower waveform, it can be seen that the same samples could have b e e n the result of sampling a faster (21MHz) signal of similar shape with the same At, and m e r e l y by looking at the screen display we w o u l d have no w a y of k n o w i n g this. In this case, the

104

Oscilloscoprs

{ ri set i rne

250 ns)

Period 1 p s

At

50

i;n4 i

4

21 MHz (risetime 12 ns)

- .-period

I I I

M!

4

47.6 ns

4

I

Figure 6.9 If the tinw inlrrval ?.I hetwrt.n samples exceeds the period of The input waveform. aliasing can result in a misleading display

1 MHz trapezoidal display created by the sampling process w o d d he a falsc display, a n ‘aliascd’ display. The cause of the tmuhlc is that for the faster signal the At i s far too large, l i r n c ~t h r clot densily rriuch too low, to build up a

proper picture of the individual signal cycles. (Tlierc is, in lacr, less than o n e dot per cycle of the 21 MHz signal.) False displays can occur with a11 waveshapes; a n aliased display of a sine wave, for exampIe, will look like another lower frequency 4ine wave. But they are freaks. The slightest change in A t in Figure 6.9 would immediately cause violent changes in the false display, causing a n incoherent jumble of dots, with perhaps successive samples taken on rising and falling slopes. The term ‘false display’ applies only to situations shown in Figure 6.9 in which the display looks misleadingly coherent and could be taken for that of a similarly shaped Iower frequency signal. As with incorrect loop gain, to guard against falsr displays thc gcncral rule is that thc dot density should hc incrcascd until n o further change of waveshape or arIipli~.udt.can be obsri-vrd. Of course, we would n o t need t o L I S ~ a sampling scope i o look at a 2 1 MHz wavcIorrn, let alonc a 1 MHz waveform, but it illustrates thc principle and emphasizes how t.he user must. bewarc of ’aliasing’. After all, if y o u wcrc using a sampling scopc

Sampling oscilloscopes 105 to view very high-frequency p h e n o m e n a and needed incidentally to check out a lower frequency waveform in the process, you might well use the sampling scope, simply to save the time and bother of fetching a real-time scope. The whole purpose of sampling is to look at or measure very fast waveforms. What determines the m a x i m u m frequency or m i n i m u m risetime that a given sampling system can handle? In a fast signal the voltage level changes very rapidly, and if it is desired to reproduce these changes on an oscilloscope display, the sampling bridge must be capable of taking discrete samples representing the various points on the ascending or descending portions of the waveform. This is only possible if the time duration during which the sample is taken is m u c h shorter than the slope to be measured. Hence the importance of providing extremely short sampling pulses, and using the fastest available diodes, but further circuit details are not appropriate in a general book on oscilloscopes, such as this. The various techniques in u s e in sampling scopes and, nowadays, in digital sampling scopes, achieve sample times short enough to provide a bandwith of up to 50GHz and a risetime as short as 7ps (see Figure 8.19). Incidentally, in sampling scopes (whether of the older analogue sort, or m o d e r n digital sampling scopes) the n u m b e r of circuit elements affected by these design considerations is relatively small, so the price of a sampling scope is mainly determined by other considerations. Sequential sampling scopes share one problem with ordinary analogue scopes. The trigger circuit cannot respond instantly to a changing signal level, such as the leading edge of a pulse, and the sweep circuitry (or in this case the fast ramp and comparator) cannot start instantly w h e n the trigger does occur. Therefore if we attempt to trigger on, and then observe, a fast signal slope, that slope will have ended before the sweep or sampling process has commenced. The solution in real-time oscilloscopes is to insert a delay line (typically 2 0 0 n s long) into the vertical signal path, with the trigger pick-off point located ahead of it. In this way, the slope of a signal can initiate the trigger before entering the delay line, and w h e n it emerges from the far end of the delay line and reaches

106

Oscilloscciprs

the vertical deflection plates the sweep will have started and the slope can be observed. The same technique can be used in sampling scopes. The delay line must be ahead of the sampling gate (see Figure 6.4) so that the first samples can be taken on the just-emerging beginning of the signal slope. But delay lines have three great disadvantages in sampling systems: 1. As they are situated at the input of the scope circuit, their characteristic impedance (usually 50 ( I ) prevents us Irom

designing input circuits of higher input impedance. 2 . The prcscnt state-of-the-art delay lines have bandwidt.hs of ,jiisl. a few GHz, a n d su in the fastest instruments. prcciscly whcrc the need Inr delay is greatesi., [.hey c a I i l i o ~be used. 3. They a r e heavy, costly and bulky. Modern sampling equipment is often designed i n niodular form: in a sampling plug-in there is often j u s t no room for a delay line of adcquatc pcrfnrmance. In sampling systems, then. delay lines often cannot be fitted for physical reasons, but if they are used, their presence will constrain the system bandwidth t o a few GHz and the input impedance to 5 0 n . " If you need t o observe the point on the waveform on which you are triggering and cannot use a system with a delay line. you will either h a w to provide a source of 'pre-trigger' (a pulse occurring ahead of the point of interest), o r you wilI have to resort to the use of 'random sampling'. Random sampling Sincc. after recognizing a trigger, thcrc must he some finite time before the firsi. sarnplr ran he iaken, i h e n exan1inin.g thc lcading r dgc w h i ch 1rigg c.r c d t 11c sa nip1c scc ms a n i 11sI I r i n n iah I e proh1c.m if a &lay liric is iriarlrnissiblc. 111 lacl, i I is i~isurrIiourit.ablc. *For i t w Tc.ktronix 1 1 8 0 1 R sarnpling oscilloscope, a 47.5 [is delay line Is availahlc, with a bandwidth of 5G11z. 'l'his is achicwrd hy hiiilding i m t rhr linc's freqiicricy-clcI)eii~leii~ l o s s t o a 'flat' ( 0 - 5 GHz) loss of 6 dB. Without t h e dday line. t h c instrument priwidcs a bandwidth of u p to 50 GHz, depending upon the plugin selected

Sampling oscilloscopes 107 Some u n i q u e leading edge of a w a v e f o r m that caused the trigger will have irretrievably passed before the sample can be taken, and we shall never see it. W h a t comes to our rescue is the fact that, in sampling, we are dealing with repetitive waveforms. We shall never see that leading edge, but if repetitive m e a n s w h a t it says there will be plenty more identical-looking ones coming along. The basic idea in r a n d o m sampling is not to take the samples extra fast, trying to win the race with the first leading edge, but on the contrary to delay t h e m until just before the next leading edge is due. The circuit in fact attempts to predict the arrival of the next leading edge and takes the next sample a little a h e a d of it. And then, of course, on subsequent signal cycles, further signal samples will be taken At later to build up the complete reconstructed image just as in sequential sampling. The reason for the t e r m ' r a n d o m ' will b e c o m e apparent after the system has b e e n fully described. R a n d o m sampling is available on some Tektronix 7000 series instruments, e.g. using the 7T11 plug-in, and currently on the 11403A Digitizing Oscilloscope, the 6GHz TDS820 Digitizing Oscilloscope and the 50 GHz CSA803 C o m m u nications Signal Analyser. In the simplified block diagram s h o w n in Figure 6.10 the vertical circuitry is the same as in Figure 6.4 except for the omission of the delay line. Blanking, gating and resetting circuits w h i c h are the same as in Figure 6.4 have, for clarity, b e e n omitted in Figure 6.10. The first i m p o r t a n t difference b e t w e e n Figure 6.4 and 6.10 is that there is n o w no link b e t w e e n the trigger block and the fast ramp. If the fast r a m p started at the time that the trigger pulse occurred (here designated to) it w o u l d be too late to catch the elusive leading edge on w h i c h we are triggering. The circuitry i m m e d i a t e l y u n d e r n e a t h these blocks is designed to produce a substitute pulse w h i c h arrives a h e a d of the trigger pulse at the time tl, sometimes k n o w n as 'prediction time' because the circuit predicts the time of arrival of the next leading edge. The heart of the r a n d o m m o d e circuits is the r a t e m e t e r ramp, w h i c h is a slow r a m p reset by the trigger hold-off circuit at a fixed time (t5) after the trigger pulse has occurred, and the r a m p t h e n begins to r u n d o w n as s h o w n by w a v e f o r m 6. It will depend on

signal

(~ trigger~[ take-offl

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tl

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to

Figure 6.i0 Provided the input waveform has a constant period like Figure 6.2, and not like Figure 6.3, then the random sampling mode can display the whole of the leading edge, by using a predicted trigger time

sampling oscilloscopes 109 the repetition rate of the signal h o w far this r a m p can r u n d o w n before the n e x t trigger occurs. W h e n it occurs, the level of the r a m p will be gated into the r a t e m e t e r m e m o r y ( w a v e f o r m 7). The d.c. level in the m e m o r y is therefore a m e a s u r e of the repetition rate of the signal, h e n c e the n a m e ' r a t e m e t e r ' . A small a m o u n t of d.c. is added to w a v e f o r m 7 a n d the result, w h i c h is s h o w n as w a v e f o r m 8, is fed to the r a t e m e t e r comparator. This compares the r a m p itself w i t h this d.c. level a n d will produce, as is clear from the w a v e f o r m illustration, a tl pulse a h e a d of the n e x t to pulse. The time difference b e t w e e n the t w o is called 'lead time' a n d expresses h o w m u c h time w e have gained, h o w m u c h s o o n e r the fast r a m p can be started t h a n in the sequential system of Figure 6.4. If the lead time is adjusted to a suitable value (by varying the a m o u n t of d.c. added to w a v e f o r m 7) w e can arrange it so that the leading edge of interest is displayed in a n y desired position, such as the centre of the screen. Should the signal repetition rate change a n d to s u d d e n l y appear earlier or later, the tl preceding it will be too late or too early respectively, but the n e w to time will gate a n e w r a m p level into the r a t e m e t e r m e m o r y , which, w i t h the addition of the usual d.c. level, will p r o d u c e the correct t~ in relation to the n e w signal repetition rate on the very n e x t cycle, assuming there are n o f u r t h e r changes in signal repetition rate. It seems a workable solution. But in fact there are problems, n o t the least of w h i c h is that few signals are as stable as t h e y appear and as we h a v e just assumed. Often signals contain incidental f.m. (frequency m o d u l a t i o n ) , w h i c h m e a n s that the distance b e t w e e n successive times to c o n t i n u o u s l y changes a n d the tl pulses p r o d u c e d on the basis of previous to times continually miss the mark. But unless the fast r a m p starts at times precisely related to the leading edge w h i c h t h e y are i n t e n d e d to sample, successive samples will n o t be t a k e n in the usual sequence along the w a v e f o r m . A n o t h e r p r o b l e m is that the r a t e m e t e r c o m p a r a t o r circuit m u s t c o m p a r e a very slow, shallow r a m p w i t h a d.c. level, a n d the slightest a m o u n t of noise on either w a v e f o r m can lead to substantial time jitter of t~. S u m m i n g up these problems, the a m o u n t of lead time is often subject to u n a v o i d a b l e variation, either because the spacing

110 Oscilloscopes b e t w e e n successive to pulses varies, or because t~ itself is n o t sufficiently stable. This m e a n s that the fast r a m p s are started inconsistently w i t h respect to the w a v e f o r m w h i c h t h e y are m e a n t to sample, a n d samples are t a k e n s o m e t i m e s too soon a n d s o m e t i m e s too late. If such samples w e r e s h o w n on the c.r.t, w i t h the n o r m a l regular horizontal spacing derived f r o m the staircase generator, they w o u l d in fact s h o w an u n t r u e , i n c o h e r e n t display. This brings us to the second m a j o r difference b e t w e e n Figures 6.4 and 6.10. The horizontal amplifier is no longer driven by the staircase generator. A timing r a m p circuit is substituted instead, w h o s e job it is to find out just w h e n , in relation to to, the sample was actually taken, and to place the dot horizontally in the appropriate position, r e p r e s e n t a t i v e of the time of sampling. In this w a y a c o h e r e n t display can be built up, even if some of the dots are laid d o w n out of sequence. In the description w h i c h follows, t2 designates the time w h e n a sample was taken. The timing r a m p circuit is a r r a n g e d in such a w a y that a r a m p starts at to or t2, w h i c h e v e r comes first, and stops at t2 or to, w h i c h e v e r comes second. If t2 is first, the r a m p runs positive; if to is first, it runs negative. W a v e f o r m 9 shows h o w this results in stopped r a m p levels w h i c h are a m e a s u r e of the time difference b e t w e e n t2 and to; they are therefore a m e a s u r e of h o w early or late the sample was taken, a n d h o w far to the left or the right of the c.r.t, screen it should be displayed. The stopped timing r a m p levels are used to drive the horizontal display amplifier. Under ideal conditions ( w h e n both the signal and tl are perfectly stable) the fast ramps will always start at the same point on the signal a n d the strobe c o m p a r a t o r will result in the usual regular series of sampling pulses occurring, on successive cycles, at progressively later points on the w a v e f o r m . Successive timing ramps will a p p e a r as in w a v e f o r m 9 and the c.r.t, display will a p p e a r as s h o w n . (Since t2 -- to corresponds to the centre point of the screen in the X direction, clearly the lead time t~ m u s t correspond to r a t h e r m o r e t h a n half the time interval r e p r e s e n t e d by the full width of the display.) But if to or t~ (or both) jitter, fast r a m p s will start at u n e x p e c t e d times, samples will be t a k e n s o o n e r or later t h a n the staircase g e n e r a t o r directs, and w a v e f o r m 9 timing r a m p s


111

r u n correspondingly higher or lower. The result is a display in w h i c h the dot spacing can vary in a r a n d o m manner, and the dots are not necessarily laid d o w n in strict sequence. It is this r a n d o m appearance of the trace that gives rise to the n a m e ' r a n d o m sampling', but the i m p o r t a n t thing to keep in m i n d is that each dot represents the signal amplitude at the instant w h e n the sample was taken and (by its correct horizontal position) the exact time at w h i c h this happened. Therefore, although dots m a y occur with r a n d o m spacing or in r a n d o m sequence, each represents a point on the signal locus, and the reconstructed trace is coherent. ' R a n d o m sampling' does not m e a n that we are attempting to take samples at r a n d o m . Nor does it m e a n that the system can cope with r a n d o m signals. We still require repetitive signals to build up a display over m a n y signal cycles, and in fact it requires m o r e stable signals t h a n in the sequential mode, because if they were not, prediction time tl w o u l d be w r o n g so often and by so m u c h that few samples w o u l d appear on the screen. Consider Figure 6.3. After each sample the ratemeter m e m o r y w o u l d adjust itself to the time interval b e t w e e n signals just experienced, but each time the next interval is quite different. So tl w o u l d never be correctly placed in relation to the n e w to. Samples w o u l d be taken at times t2 that were vastly too soon or too late, causing the timing ramp to r u n so high or so low that (quite correctly) the dot w o u l d be driven off-screen. One final element of the block diagram, the dot position differential comparator, needs to be explained. It was said earlier that the a m o u n t of d.c. added to w a v e f o r m 7 determines h o w m u c h lead time is produced. Now for an i n s t r u m e n t covering a wide range of sweep speeds and i n t e n d e d for looking at a wide range of signal frequencies, no one fixed a m o u n t of lead time can be appropriate for all conditions. One could provide a potentio m e t e r with w h i c h the user w o u l d be able to adjust the lead time (the a m o u n t by w h i c h the user wants to see ahead of the triggering point). But with a simple servo loop this operation can be automated. It is assumed that most users, most of the time, like to have half a screen width of lead time, so that the leading edge of the

112 Oscilloscopes w a v e f o r m appears in the screen centre, just as illustrated in Figure 6.10. Consider w h a t is needed to achieve this, and assume for simplicity that the trigger to occurs halfway up the slope of the leading edge. The sequence of samples produced from left to right in Figure 6.10 is the result of the staircase generator running up (waveform 5 in Figure 6.4). We w o u l d like t~ to have such a lead time over to that the sample taken w h e n the staircase generator is at the halfway mark occurs halfway up the leading edge of the signal. (In other words, at the staircase halfway point t2 should occur at to.) Now for each sample taken, the stopped level of the timing ramp expresses w h e n tx actually occurred in relation to to. If t2 and to coincide, the stopped level of the ramp is represented by the central one of the nine stopped levels s h o w n in waveform 9. It can therefore be said that if the lead time is correct, the halfway level out of the staircase generator will result in the halfway level out of the timing ramp circuit and there will of course be a similar correspondence between the other steps of the staircase and the other stopped levels of the timing ramp. We could arrange a differential comparator in such a way that w h e n these conditions exist it produces a nominal d.c. output which suits the adder. But if t~ does not occur at the correct time to produce this result, then the timing ramp level will be different. To remedy the situation, the differential comparator, which compares the staircase level (representing the desirable condition) with the timing ramp level (representing the actual condition), produces a n e w d.c. o u t p u t of such polarity that waveform 8 is appropriately raised or lowered to correct the lead time. It was pointed out earlier that the dots may well be laid d o w n with u n e v e n spacing or out of sequence as a result of t~ or to jitter. Obviously, then, the timing ramp levels will also show this erratic behaviour, and if the serw~ loop attempted to correct for each individual error, each time the timing ramp differed from the idealized staircase generator level, it would merely add a n o t h e r variable to the already varying to and t~, causing even greater jitter. This is not the purpose of the servo loop. It is intended to correct for long-term drift or for changes in the selected display speed in such a way that the leading edge is held at screen centre.


113

The servo loop time constant is therefore made deliberately quite slow, typically b e t w e e n 0.1 and 1 second, so that it will not contribute in any w a y to the time jitter of t l. A few anomalies w h i c h occur in r a n d o m sampling e q u i p m e n t must be m e n t i o n e d . First, the ratemeter ramp, although it is a slow ramp, will sooner or later ' r u n out of steam' as it reaches the negative p o w e r supply voltage, and if the signal repetition rate is so low that to has not occurred before this time, the circuit will of course fail to operate correctly. A typical lower signal frequency limit in the r a n d o m m o d e is 100 Hz. A second point concerns smoothing. This condition requires, it will be recalled, that sufficient samples are taken on the same portion of the signal to allow the circuit to attain the correct level. (With a loop gain of one-third, at least twelve samples were needed to get within 1 per cent.) But if to or tl jitter and cause successive samples to be taken out of sequence at different points on the signal, t h e n the circuit will never have a chance to reach the correct level and the display will appear to break up. Given a noticeable a m o u n t of ' r a n d o m n e s s ' due to to or t~ jitter, the r a n d o m m o d e therefore demands that the loop gain be absolutely correct: every single sample taken m u s t correctly represent a point on the signal w a v e f o r m if the display is to be coherent. One can t u r n this b e h a v i o u r to advantage w h e n adjusting the dot response control. As it is rotated, an obviously incoherent display will become coherent at the point w h e r e the dot response is correct. Another side effect of r a n d o m n e s s is that kickout will become more noticeable. It was stated earlier that one of the advantages of the feedback m e m o r y is that the voltage level at the o u t p u t of the sampling gate will be approximately the same as the signal level w h e n the n e w sample is taken, hence very little energy needs to be transferred w h e n the sampling gate conducts. Now, with r a n d o m sampling, if successive samples are taken at quite different points on the waveform, the voltage levels will not be the same (since the voltage level b e h i n d the gate corresponds to the voltage level on the previous sample) and therefore m o r e energy needs to be transferred; kickout is significantly greater.

I I4

Oscilloscopes

The r a n d o m m o d e was i n v e n t e d to allow us to see the leading edge of signals w h e r e n e i t h e r a pre-trigger pulse n o r a delay line can be used. It p e r f o r m s this function, but at the obvious cost of m u c h added circuitry, a n d can only p e r f o r m well with stable signals. It m u s t be concluded therefore that the wise user only employs this m o d e of operation w h e n , for the stated reasons, it is necessary to, a n d switches in all o t h e r cases to the n o r m a l sequential sampling m o d e w h i c h r a n d o m sampling scopes also provide. Finally, it m u s t be added that n e i t h e r in the sequential nor the r a n d o m sampling m o d e does the user have to look at or n e a r the triggering point of the signal w a v e f o r m . Controls are provided to delay the sampling pulses so that a n y desired portion of the signal can be observed. But pressure on space prevents a detailed discussion of h o w this is done.

7

Digital storage oscilloscopes Since they were first introduced in 1971, the design and performance of digital storage oscilloscopes - DSOs - has advanced immeasurably. Furthermore, the pace of d e v e l o p m e n t has quickened perceptibly in recent years. So in the fourth edition of this book a chapter was devoted entirely to them. However, even so it is only possible to cover their design and uses in a fairly brief way. Readers requiring a book covering the subject in greater depth should consult Digital Storage Oscilloscopes, B u t t e r w o r t h - H e i n e m a n n , ISBN 0 7506 2856 1, by the same author. The circuitry of conventional real-time oscilloscopes - the ' h o w they w o r k ' - together with the construction of the c.r.t.s they use are covered in Chapters 9 to 11, but in this chapter I have followed the same plan as the preceding one on sampling scopes: details on the m e a s u r e m e n t m e t h o d s available with DSOs and on h o w they are i m p l e m e n t e d by the internal circuitry of the scope are all covered in one chapter. Figure 7.1, then, is a simplified block diagram of a basic DSO. Comparing it w i t h t h e block diagram of a real-time analogue scope, see Figure 2.1, will show considerable similarities: the major difference is that the vertical signal, after passing t h r o u g h the input attenuator, Y preamplifier and trigger pick-off stage, is not routed directly to the Y deflection stage. Instead it is sampled at intervals and the samples fed to an ADC to be 'digitized', i.e. converted to a string of numbers: each n u m b e r represents the voltage of the input signal at the instant the corresponding sample was taken. The digitized data is stored in a 'channel store', i.e. that part of the total digital m e m o r y w h i c h is allocated to the particular Y input channel, of w h i c h there are usually at least two and often more. The digital m e m o r y consists of a bank of RAM ( r a n d o m access m e m o r y ) ICs (integrated circuits).

116

Oscilloscopes i

input and

I

"

J

trig pick off amplifiers

Jvotts/d,v m-~

,~

'

I

IJ

9

il I

I

Y2

,~

buffer

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9

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=nput

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capac t o

~

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r

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-

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from

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I

r ~ ' - ~ ,:,";cTo, V

cons,o=

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-

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r

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CRT EHT

deflection amphfier

Figure 7.1 Simplified outline block diagram of a [ypical DSO (digital storage oscilloscope)

For display purposes, the data c u r r e n t l y in the store is read o u t sequentially a n d the samples passed to a DAC - a digital-toa n a l o g u e converter. There t h e y are r e c o n s t i t u t e d into a series of discrete voltage levels f o r m i n g a stepwise a p p r o x i m a t i o n to the original w a v e f o r m . This is fed, along with the r e c o n s t i t u t e d w a v e f o r m s ( s ) from the o t h e r Y channel(s), to the vertical deflection amplifier for the usual dual or four trace display. Note that the r e a d o u t and display of samples constituting the stored w a v e f o r m n e e d n o t occur at the same sample rate that was u s e d to 'acquire' the w a v e f o r m in the first place. It is sufficient to use a display sample rate a d e q u a t e to e n s u r e that each a n d e v e r y trace displayed is r e w r i t t e n fifty or m o r e times a second; this will p r e v e n t flicker of the display. This m e a n s that in principle, as w e saw with sampling scopes in C h a p t e r 6, o n e could use a Y deflection amplifier and c.r.t. (or LCD display panel) with very m o d e s t b a n d w i d t h as the display in a DSO, e v e n t h o u g h the i n s t r u m e n t as a w h o l e is capable of displaying signals w i t h a b a n d w i d t h of tens or e v e n h u n d r e d s of m e g a h e r t z . In practice,

Digital storage oscilloscopes 117 however, some DSOs are also capable of being operated as conventional real-time oscilloscopes, with a bandwidth in this mode equal to their bandwidth in digital mode. A good example is the Fluke PM3370, with a real-time analogue bandwidth of >60MHz, and a m a x i m u m digitizing rate of 2 0 0 M s / s (megasamples per second) single shot, 10Gs/s in equivalent time repetitive mode, see Figure 1.5. There are very real advantages to such a 'dual purpose' instrument, as will become apparent later in the chapter. But there is a n o t h e r approach. A m a n u f a c t u r e r m a y elect not to equip a DSO with a real-time analogue capability at a l l - in which case all signals displayed are reconstituted from the stored data. In such instruments the display tube is often a raster scanned, magnetically deflected c.r.t., either m o n o c h r o m e or c o l o u r - the technology of a TV display, or maybe an LCD type, either m o n o c h r o m e or colour. In this case, the display m a y be 'bit mapped', which requires more m e m o r y than other types of DSOs, but which greatly expands the range of display possibilities. The DSOs in the Hewlett-Packard range are good examples of this type of instrument; see, for example, Figure 7.3. Note that with both the dual purpose and the digital-only instruments, h o w e v e r high the sampling rate (and allowing for 'equivalent time' time sampling, of which more later) the Y b a n d w i d t h can never exceed that of the input attenuator and Y preamplifier. Likewise, h o w e v e r great the vertical resolution (however m a n y bits the ADC outputs per sample), the vertical m e a s u r e m e n t accuracy will be limited by the linearity (freedom from distortion) of the Y preamplifier and the ADC. Furthermore, w h e n a dual purpose i n s t r u m e n t is used in the analogue mode, the horizontal accuracy will be limited by the timebase, X amplifier and c.r.t, linearity to a r o u n d 2 per cent. By contrast, in digital storage mode, the measurement (as distinct from the display) accuracy in the X direction will usually be 0.01 per cent or better. So m u c h by way of introduction; n o w let us look at the various operating modes of DSOs, h o w they w o r k and the implications for the user.

118 Oscilloscopes

Roll mode We will sr.art. w i ~ hroll rnc.)de, no1 becairse i I is 1 . 1 1 ~most useful modc but because it h a s been availablc on DSOs from an early stage, 1)rt.ause iI is IIIn d a riieii rally di fl'errri I f r o m a (-(.In ve 11 I iona I scope display and because it will lead in nicely tu the other operating modes of DSOs. For simplicity, consider a DSO with 1024 points of memory per input channel, typical of the lower to middle range of jnstruments. Some DSOs display the 1024 points across the usual ten horizontal graticule divisions, while others overscan b y 2.4 per cent, giving exactly 100 points per graticule division - t o simplify the numbers in the following explanations we will assume the latter. Roll mode operation is rather like a chart recorder, where a trace is written on a strip of paper being drawn at a steady rate from a roll of chartpaper. Imagine the paper moving from right to left and y o u have a n analogy of roll mode. The trace on the scrwri o f lhe oscilloscope appears l o be written by a 1 ~ 1 hidden 1 j u s t t o the right of the screen and the display scrolls across disappearing o f f thc lcft of tlic. S C ~ C ' C ' I I111 . fact, inlorrnatioii or1 tlic part of the rvavcforni o f f the screen t o the left is losi: it docs not pilr U I I 0 1 1 rht. rloor like lie paper lrorri a charl recorder would. Figurc 7.2 shows a n indctcrminatc wavclorm which could corresporid t o arty pliysical variable - i t ntight, lor example, be the o u t p u l volldge o f a load-bearing transdiicer measuring the stress at o n e point of a bridge as traffic passes over. Let us assume that the DSO is set up t o take 100 samples per second, then after (just over) ten seconds i t will have filled up the 1024 memory locations - which are numbered 0 to 1023 - a s at A in Figure 7.2. Ten milliseconds later it will be time t o take another sample. But before doing so. the digital representations of the samples currently in store in locations 0 to 1023 are read o u t one after the other and passed in turn t o the D A C which turns t h e m back into voltage levels. These are displayed sequentially across the screen from lrft t o right, thus displaying the first tcn second segment of the waveform. Another sample is now taken - but locations 0 t o 1023 are already full arid there is 110 storage location 1024. 50 Ihis new sample is stored i n locat.ion 0, overwriting the digit.al value

Digital storage oscilloscopes I19 previously stored there. This n e w 'sample 0' corresponds to a point in time a b o u t ten seconds later t h a n the previous sample 0, as at B in Figure 7.2. The c h a n n e l m e m o r y is thus cyclic; like a loop of recording tape, earlier i n f o r m a t i o n is replaced cont i n u o u s l y by later, as indicated in Figure 7.2. As soon as the n e w sample is stored in location 0, all the stored sample values are cycled t h r o u g h the DAC a n d displayed again, this time starting w i t h location 1 at the left of the screen a n d c o n t i n u i n g t h r o u g h to location 1023, finishing up w i t h location 0 (the last sample acquired) at the right of the screen. The trace displayed is thus the

voltage trigger-' level c

10

0

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20 seconds

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1

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0 1 1023=~ 2_etc . . . . . . .

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X

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j I I t'

in a c o n v e n t i o n a l 'scope)

Note: sampling ceases at point X

write ~ J

Figure 7.2 Roll mode

read

cessation of

II

sampling

~ delayed

I

100% post trigger I greater than 100% post t r i g g e r j

(equivalent to delayed sweep

s a m p l i n g ceases as soon as t r i g g e r detected

• I •

I

i

120 Oscilloscopes same as previously, but s h u n t e d to the left (on the screen) by one sample position. The allocated RAM ( r a n d o m access m e m o r y ) storage locations are as at B, or after the next sample, as at C, etc. After 512 samples, the original r i g h t - h a n d edge of the trace will h a v e w a l k e d across to the middle of the screen, while the lefth a n d half of the original trace will have disappeared for ever. Alternatively, a display ' w i n d o w ' 10.24 seconds long can be considered as advancing along the w a v e f o r m (see D in Figure 7.2). The i m p o r t a n t point to bear in m i n d is that each time the trace is w r i t t e n to the screen of the c.r.t, the samples stored in all 1024 locations are displayed; starting at the left of the screen w i t h the oldest sample and finishing at the right with the sample just taken. Figure 7.2 shows at J the c h a n n e l m e m o r y r e d r a w n as a circular track, with the store input (write) switch and store r e a d o u t switch of Figure 7.1 d r a w n like the h a n d s of a clock. The write switch will usually rotate continually at a constant speed. The read switch will in all probability rotate at a quite different speed and, as we have seen, not necessarily at a constant speed at all. Each ' h a n d ' w o u l d typically be an eight bit wide data bus: in the case of a m e m o r y consisting of dual port RAM this w o u l d be quite a good analogy. However, dual port RAM is expensive a n d in practice ordinary CMOS, NMOS or ECL static RAM, or in the lower-priced i n s t r u m e n t s , d y n a m i c RAM, is used instead. This has a single r e a d / w r i t e data port, which is switched b e t w e e n the two functions by an R/W control line. With the slow data rate in the e x a m p l e just given, there would be no difficulty at all in interleaving the write and read functions, even with relatively slow, cheap, d y n a m i c RAM. If the sample rate w e r e slower t h a n the 100 s/s considered above, the screen trace w o u l d be r e w r i t t e n twice or m o r e b e t w e e n each sample, to m a i n t a i n a high e n o u g h screen refresh rate to aw~id flicker. On the o t h e r hand, at m u c h higher sample rates, several or m a n y samples could be t a k e n before rewriting to the screen. R e t u r n i n g to the w a v e f o r m in Figure 7.2, it is clear that at a n y time there is a record of the last 10 seconds of the w a v e f o r m in store. This i n f o r m a t i o n can be frozen at any time if an event of particular interest o c c u r s - such as a dangerously high stress in the

Digital storage oscilloscopes

121

bridge due to an overloaded lorry in our fictional example. We can set the DSO's trigger circuitry so that if the Y input voltage exceeds a certain level, the sampling action is h a l t e d - the write h a n d in Figure 7.2 J ceases to rotate. Furthermore, although the read h a n d continues to rotate, thus continually displaying the stored trace on the screen, since the trace displayed always starts at the left of the screen with the oldest sample last taken, the trace is n o w stationary. Like the flight data recorder in a crashed plane, the trigger event has terminated the recording of data, rather t h a n initiating it like the trigger circuitry in a conventional real-time scope. Imagine the flight data recorder uses a loop of tape holding data on just the last ten minutes of any flight, and the analogy is perfect. This type of operation is k n o w n as 100 per cent pre-trigger store and is illustrated in Figure 7.2 E. In the flight recorder example, the trigger event was effectively the end of the world, but in our DSO, we c a n arrange the circuitry to take some samples after the trigger event before terminating the sampling process. A n o t h e r 512 samples, as in Figure 7.2 E will lose the oldest 50 per cent of the pre-trigger information but store five seconds w o r t h of the w a v e f o r m post-trigger. By suitable settings of the controls we can, in principle, have any split we w a n t b e t w e e n pre- and posttrigger information, or set an even greater delay in terminating sampling, as in Figure 7.2 E to H. In practice, DSOs usually offer the choice of a small n u m b e r of settings such as 100 per cent, 75 per cent, 50 per cent and 25 per cent pre-trigger storage, while only the more expensive instruments provide delayed (greater t h a n 100 per cent post-trigger) storage. We m a y still wish to capture an event w h i c h triggers the scope, but with greater time resolution t h a n provided by the 100 sis in the roll m o d e example above. But at 100 ks/s, say, giving a time resolution of 10 ~s in the stored trace, the w a v e f o r m w o u l d be rushing across the screen so fast as to present a meaningless jumble to the observer. In this case, triggered storage mode, also k n o w n as single sweep or single shot, is m o r e appropriate. The DSO operates in exactly the same w a y as in roll m o d e except that the w a v e f o r m being acquired is not displayed until the trigger event stops the sampling clock. An ' a r m e d ' indicator is often p r o v i d e d - this is illuminated to indicate that the scope is

122 Oscilloscopes

Figure 7.3 The Hewlett-Packard Infiniium range of oscilloscopes includes this model 54845A, with its 1.5 GHz bandwidth. It samples at 4 Gs/s simultaneously on all four input channels, or at 8Gs/s in two channel mode (reproduced by courtesy of Agilent Technologies, the new name of Hewlett-Packard Measurements Division)

c o n t i n o u s l y a c q u i r i n g t h e i n p u t signal. W h e n t h e trigger e v e n t occurs, t h e a r m e d light goes o u t a n d t h e s a m p l i n g clock is s t o p p e d , e i t h e r i m m e d i a t e l y or w h e n t h e d e s i r e d a m o u n t of posttrigger i n f o r m a t i o n has b e e n s t o r e d - a ' s t o r e d ' indicator (if p r o v i d e d ) t h e n lights. A reset or release b u t t o n is p r o v i d e d to r e a r m t h e s y s t e m , r e a d y to stop o n t h e o c c u r r e n c e of a n o t h e r trigger e v e n t . O p e r a t i o n is v e r y similar to t h a t of t h e single s h o t m o d e in a c o n v e n t i o n a l scope w i t h c a m e r a or an a n a l o g u e (tube) s t o r a g e oscilloscope, with t h e big difference t h a t w i t h t h e s e o n e cannot capture pre-trigger information.

Refresh m o d e It was m e n t i o n e d earlier t h a t w h e n t h e s a m p l e rate (the e q u i v a l e n t of t i m e b a s e s p e e d in o r d i n a r y scope p a r l a n c e ) b e c o m e s too high, t h e display in roll m o d e is n o l o n g e r useful. A n a l t e r n a t i v e to single shot o p e r a t i o n in this case is refreshed or recurrent m o d e ; u n f o r t u n a t e l y t h e t e r m i n o l o g y relating to this m o d e , as w i t h o t h e r m o d e s a n d f u n c t i o n s of DSOs, varies f r o m

Digital storage oscilloscopes 123 m a n u f a c t u r e r to manufacturer. This m o d e is particularly useful w h e n the w a v e f o r m of interest is repetitive, or very nearly so. With it, the DSO produces a stable, triggered display looking very like the display on an analogue scope. The w a v e f o r m is, however, still being acquired continuously, so that w h e n e v e r sampling is stopped, a s e g m e n t of the w a v e f o r m preceding that instant is held in store. Of course it is unlikely that the screen display will correspond exactly to an integral n u m b e r of cycles of the input w a v e f o r m (see Figure 7.4(a)), w h e r e the screen is s h o w n as displaying about 1~ cycles. So here, half a cycle or so is not being displayed each time the trace is written on the screen. This seems to contradict the earlier s t a t e m e n t that the input signal is being acquired continuously. But acquisition and display are

f

7-1

trigger level

b

c

(a) C

1023 0

increasing

~

acquisition store

(b) Figure 7.4 Refresh mode

display store

124 Oscilloscopes n o t the s a m e thing. The signal is a c q u i r e d c o n t i n u o u s l y in a 'cyclical' acquisition m e m o r y like t h a t s h o w n in Figure 7.2 J but the display is fed f r o m a separate display m e m o r y . This is indicated in Figure 7.4, w h e r e (a) s h o w s the display while (b) s h o w s h o w the m e m o r y transfers are organized. The digitized w a v e f o r m is fed c o n t i n u o u s l y into the acquisition store so that at p o i n t c the data o v e r w r i t e s that p r e v i o u s l y stored t h e r e at time a - time has b e e n d r a w n increasing as a spiral so that this can be s e e n m o r e clearly. If the trigger circuit has b e e n set to detect the positive-going edge of t h e w a v e f o r m at a, t h e n each of the n e x t 1024 samples stored in the acquisition store will be read out again i m m e d i a t e l y and be stored also in the display store. The display store t h e n stops accepting data f r o m the acquisition store and retains a s n a p s h o t from a to c of the r e c u r r e n t w a v e f o r m . The trigger circuit w o u l d h a v e d e t e c t e d the positive-going edge at b, but it was i g n o r e d as t h e r e was already a ' s w e e p ' in progress. Now, t h e ' r e a d o u t switch' transferring data out of the acquisition m e m o r y to the display store c o n t i n u e s to 'rotate' in s y m p a t h y with the acquisition store write switch, i n d e e d (except in the case of dual port RAM) t h e y are the s a m e t h i n g - the acquisition m e m o r y r e a d / w r i t e bus.* So w h e n the next trigger e v e n t occurs at time d, the following 1024 samples are stored also in the display store as previously. However, as the display store address c o u n t e r stopped clocking up after filling location 1023 on the last 'sweep', the 1024 samples starting at position d in the acquisition m e m o r y are stored in positions 0 to 1023 in the display m e m o r y . Thus a l t h o u g h the s e g m e n t of w a v e f o r m c to d was n o t displayed, it w a s acquired. A s e p a r a t e trigger at a h i g h e r level m a y have b e e n set to stop acquisition on, or shortly following, a positive- or n e g a t i v e - g o i n g glitch. If such a glitch o c c u r r e d in an u n d i s p l a y e d portion of the w a v e f o r m such as c-d, it w o u l d duly a p p e a r on the frozen display w h e n the last *The acquisition memory read and write 'switches' can in fact be in different positions, or even 'rotate' at different speeds as described in the section on roll mode, simply by supplying different memory addresses (which may also be incremented at different rates) depending upon whether the R/W line is at logic 1 (high) for a read or logic 0 (low) for a write cycle.

Digital storage oscilloscopes 125 acquisition was transferred to the display m e m o r y . (Glitch capture is an i m p o r t a n t topic to w h i c h I shall r e t u r n later.) This a r r a n g e m e n t provides stable, triggered viewing of a recurrent w a v e f o r m while retaining the latest acquisition of that part of the w a v e f o r m (between c and d in Figure 7.4) w h i c h was not displayed. But in fact, while entirely feasible, few if any DSOs appear to offer this facility, any information occurring on that part of the w a v e f o r m not appearing on the screen in refreshed m o d e being lost. This is more i m p o r t a n t t h a n might appear at first sight, for the following reason. The non-displayed part of the w a v e f o r m m a y be likened to that occurring during the retrace or flyback time in a real-time scope. Now, in the latter, the flyback time m a y a m o u n t to only a few per cent of the sweep time (though it can be deliberately e x t e n d e d w i t h hold-off), while in a DSO the dead time b e t w e e n sweeps m a y a m o u n t to as m u c h as several times the sweep time itself, especially if the i n s t r u m e n t uses a not very powerful microcontroller, or there is a lot of processing to do while transferring data from the acquisition m e m o r y to the display memory. While refreshed or recurrent m o d e is useful for waveforms too fast to be satisfactorily viewed in roll mode, there is a limit to h o w short a time/div setting it can support while capturing the w a v e f o r m continuously in the w a y we have considered so far. Consider, for example, a DSO with an ADC w h i c h takes 100 ns to convert a sample of the input w a v e f o r m to the corresponding digital representation, limiting the sampling rate to 10Ms/s. Assume the acquisition and display m e m o r y each have 1024 points as in the earlier example. Then w i t h 1000 points for the 10 horizontal graticule divisions, there will be 100 display points per division and with 100 ns m i n i m u m per point, the fastest available display speed will be 10 b~s per division. Depending on h o w the points are displayed on the screen (as separate dots, joined by straight lines, or by a 'sine interpolator' of w h i c h m o r e later), this will enable us to display waveforms of up to, say, 3 MHz at most. This is described as the 'single shot' or 'real-time' b a n d w i d t h . But the b a n d w i d t h of the c o m p o n e n t s preceding the ADC - the input attenuator, the Y preamplifier and the sample and h o l d - will n o r m a l l y greatly exceed this. Given the input signal is repetitive,

126

Oscilloscopes

it i s possible to capitalize on this and produce a much greater cffcctive bandwidth. In this ’sequential’ mode, t.lie DSC) docs riot capiiirc complete chunks of wavcforni in rcal time as .in Figure 7.4; the waveform is acquired in parts at successive acquisitions, or in ’equivalent time’, resulting in a considerably enhanccd sequential o r equivalent timc bandwidth. Equivalent time (sequential) mode Continuing with our previous example of a 1 0 M s / s ADC, imagine that w e select a timebase of 100ns/div. Then the ADC will only take one sample per division, whereas we wish to display 100 samples/div as previously. Furthermore, there will of course usually be no exact relation between the frequency of the input waveform and that of the sampling cIock. So the output from t h e trigger circuit might be just in time to catch the next sampling pulse, or might just miss it, or might occur midway between trvo samples. Accordingly, the saniple i n the leltniost tenth of the screen oughl t o be displayed at the left, right or middle of that horizontal graticulc division rcspcctivcly. N o w at. 100 nsidiv, 100 pointsidiv corresponds to a timc pcr point uf just. 1 11s. Conccptually, the sampling clock for thr acquisition inemory is running a l I G H z s o Ihal the write swilch sweeps round all 1024 locations in (just over) 1 p,s, but as the ADC is only laking 10 ~ V s i s .it deposits a digital sample in only every hundredth memory location, as indicated in Figiirc 7.5(a). However, will it be in the first, second, fiftieth or ninety-ninth location of every hundred? The solution t o this problem is also the answer EO the rather impractical requirement for a 1 G H z clock - I said it was only conceptual. (Nevertheless, DSOs commonly describe themselves as having a n equivalent sample rate of however many Gsamplesis or GHz effective sample rate.) The 1 0 M H z sample clock i s n o longer fed to the LSB (least significant bit) of the acquisition store address counter but t o a more significant stage so t h a t (say, for simplicity of explanation) just ten cycles take the writc switch right round the store. The trigger pulse s l a m a timer - i t could be a last ramp such as was discussed in Chapter 6 011 sanipling scopes - which measures thc dclay hcforr t h e next 1 0 M H z clock pulsc arrives. This delay is converted to a nurnhrr

Digital storage oscilloscopes 127

(a)

1St cycle r]

[1

2nd cycle.,

~--[

3rd cycle __~

o,.

[7

[-'1 [7

M

,,[1

.....

,

[-1

[-I

J-'~~

I--I

I-I_

Figure 7.5 Multiple point random sampling acquires several points in one acquisition cycle, thus reducing the acquisition time considerably. In this mode a typical DSO would acquire a minimum of 10 points per cycle, so it would reduce the acquisition time by at least an order of magnitude over a scope that acquires a single point on each cycle (courtesy Tektronix Inc.)

in the r a n g e 0 to 99 a n d a d d e d to e a c h address count. Thus e a c h of the t e n s a m p l e s following a trigger pulse is distributed e v e n l y across the acquisition store a n d h e n c e across t h e display store a n d screen, b u t correctly p o s i t i o n e d according to h o w s o o n after t h e trigger the first of the g r o u p t e n samples occurred. With no exact r e l a t i o n b e t w e e n the s a m p l e clock f r e q u e n c y a n d the f r e q u e n c y of t h e i n p u t signal, it is m o s t u n l i k e l y t h a t t h e n e x t trigger pulse will p r e c e d e a s a m p l e clock pulse by exactly t h e s a m e a m o u n t as last time, so n o w a n o t h e r t e n points will be d e p o s i t e d in t h e a p p r o p r i a t e screen positions, adding a bit m o r e definition to t h e w a v e f o r m in store, a n d so o n for e a c h succeeding trigger pulse, Figure 7.5. As m o r e a n d m o r e of t h e c o m p l e t e p i c t u r e is built up, it b e c o m e s m o r e a n d m o r e likely t h a t a g r o u p of t e n points will duplicate a n earlier set, so t h a t after 100 acquisitions, t h e picture will still n o t be c o m p l e t e . But a g r o u p of t e n points is a c q u i r e d for e v e r y trigger pulse so in just a few milliseconds, t h o u s a n d s of groups of t e n points will h a v e b e e n a c q u i r e d a n d the picture will be c o m p l e t e . This is so fast as to a p p e a r i n s t a n t a n e o u s to the eye. The e x c e p t i o n to this is t h e case w h e r e w e are using t h e 100 n s / d i v s w e e p s p e e d in o r d e r to see a

128

Oscilloscopes

narrow pulse which has in fact a low repetition rate. Here, although it only takes 1 ps to acquire ten points o n the waveform, the scope has to wait a while for the next trigger pulse, w h en it will collect the next 10 points. In this case, you may actually see thc wavcforrn picture building up slowly before your eyes, or alt.ernat.ively, wait a long rime before thc instrument is ready to upc1at.e the scrctcn display. Thc cquivalcnl time t~ iode of operation just described is called iiiulliplr point. random sarnpling. It is not too unlike the random sampling mode of a sampIing scilpc described in Chapter 6 exccpt that several points arc acquired for each trigger pulse rather than just one. The advantage of multiple point sampling whe n cxarnining a low repetition rate pulse train is obvious. You can see how, by using equivalent time sampling, a DSO operating in sequential mode can offer a bandwidth much higher than the frequency of the sample clock, limited ultimately by the bandwidth of the Y preconditioning stages - the attenuator, input preamplifier and the sample and hold. The bandwidth of these is sometimes quoted as the ’analog bandwidth’ in a DSO specification, even where the instrument uses a raster scan display and consequently only displays stored waveforms - i.e. has n o realtime analogue scopc mode. Where a high reaI-time (single shot) bandwidth is required, equivalent time sampling does not fill the hill. The ohvious way forward is t o use a faster AT)(:. Analogueto-digil.al convcrters opctrating at 500 Ms/s arc available in a n m i h c r of DSOs, whilc 2500 M s / s AnCs reprrsrlit about the currmt state o f ~ l i ra r t . Such high spccd operation is now available even i n hand-held oscilloscopes. Swnciirr~cs,in a two rhannrl instrument, thcsc can both be dedicated t u a single channel w h r n necessary, and usctd altcrnatcly intcrlcavcd at maximum speed t o provide a 5 C H z real-time sampling rat.e. Similarly, in a four channel instrument, by borrowing the other three ADCs, one could have a 10 GHz sample rate, albeit on but a single channel. There are two main types of ADC, t h e ’flash’ type and the successive approximation type. The former produces a t its output, a t any instant, a digital code corresponding to the voltage a t its input: this type is popular in high sampling rate applications,


129

t h o u g h it is usually limited to eight, seven or even just six bit resolution. The type of ADC using an S A R - successive approximation r e g i s t e r - takes rather longer to m a k e a conversion but m a y have a n y t h i n g from 10 to 16 bit resolution, and in DSOs, ADCs with such high resolution are occasionally used. Clearly there w o u l d be problems if the input voltage were to change during the conversion process, so an SAR ADC is used in conjunction with an S & H (sample and hold) circuit, as indicated in Figure 7.1. Figure 7.6 shows how, on c o m m a n d , an S & H holds the signal at the sampling instant constant while the ADC performs its conversion, and t h e n switches back to track m o d e in w h i c h it acquires and t h e n follows the current input voltage. (In Figure 7.6, the inaccuracies have b e e n deliberately exaggerated for clarity. An S & H is simply a track and hold circuit which is switched back to hold m o d e as soon as it h a s a c q u i r e d

the current

analogue

types of ADC face a trade-off between

input signal

/ ~

I

output signal

t

~

acquisition

settling ~ time

acquisition turn on delay

gate signal---

~

"'"/t----.,

--hold--=, ~ - - - - t r a c k

and accuracy on

output change caused by input change times feedthrough attenuation I droop in I droop in t~'9--hold l hold

.._aperture sample or

TTL

input voltage level.) Both resolution

-'-time delay (T a ) =

~

T

/!

|

......

hold

cycle time I logic 0 '1---logic 1

---'~- '~ =- -= =.

,

.sample

J

Figure 7.6 The elements that make up the acquisition cycle of an ADC. The turn-on time or the time that the device takes to get ready to acquire a sample is the first event that must happen. The acquisition time is the next event that occurs. This is the time that the device takes to get to the point at which the output tracks the input sample, after the sample command or clock pulse. The aperture time delay is the next occurrence. This is the time that elapses between the hold command and the point at which the sampling switch is completely open. The device then completes the hold cycle and the next acquisition is taken (courtesy Tektronix Inc.)

130 Oscilloscopes t h e o n e h a n d a n d speed on the other, w h i c h is w h y DSOs using CCDs w e r e at o n e t i m e popular. DSOs with CCDs Charge coupled devices (CCDs) h a v e b e e n available for some years. They are s a m p l e d a n a l o g u e clocked delay lines in w h i c h a p a c k e t of charge, r e p r e s e n t i n g the a m p l i t u d e of the input voltage at a n y instant, can be s h u n t e d along from o n e stage to the n e x t at each s u c c e e d i n g clock pulse. The samples e v e n t u a l l y e m e r g e after a delay equal to the clock period times the n u m b e r of stages in the line, usually 512 stages. C o n t i n u e d d e v e l o p m e n t has raised the m a x i m u m o p e r a t i n g clock f r e q u e n c i e s of such devices to 4 0 0 M H z . The b e a u t y of the s c h e m e is t h a t a single shot b a n d w i d t h of well over 100 MHz (with sine interpolation) can be o b t a i n e d with a relatively slow ADC. This is a c h i e v e d as follows. W h e n a trigger e v e n t stores a h i g h - s p e e d transient, it does so by stopping the CCD clock. This freezes a string of 512 a n a l o g u e

Figure 7.7 Tile DL7100 Signal Explorer provides a 500MHz bandwidth and sensitivities to 2 mV/div. Two Y input channels arc supplcnlenled by two 8 channel logic inpuls. Ot use when viewing jittery wavcfornls, cc)lour accumulate and persistence mode distinguishes frequency of event occurrence by colour (reproduced by courtesy Yokogawa Martron Lid)

mux

demux interleaved data buses

Ill""~ iLl I11~ I

8 ~,ll

8

i '~

"" '"ill"

,. 81

analo;ue

I

input

9

~%

./% . . . . . . .

J~L__

J

8'

data 8

,

L

,8

,8

t-

i

,'8

,8 to

r

O .B

display section

i

_

sample clock

~

!

,~f~

cr u

M i

address and R/W control

T

l

1

l

display

timing control

Figure 7.8 Outline schematic showing how the acquisition memory RAM can handle up to four times the data rate of the individual RAM [Cs. Further subdivision to eight banks and/or dual port RAM would provide even greater speed

132

Uscilloscopcs

samples in thc CCD delay line. A lower frequency clock is now applicd so that insiead ol spilling our of r.he end of the CCD delay line ar up to 400Ms/s, the samplcs now tricklc nut at a rate within the capabilities or a fairly rnodesl, inexpensive ADC. In ryfieshed mode, the ADC converts only every umpteenth sample from the delay line (via a n S 6. H), building up the picture in equivalcnt timc, whcncvcr the CCD clock frequency exceeds the maximum ADC conversion rate. At lower clock rates, such as in roll mode, the ADC can cope with all the samples o u t of the CCD delay line as they arrive. As the performance of high speed ADCs has advanced and their price fallen, the use of CCDs (which have been developed to the limit of their capabilities) in DSOs is becoming a thing of the past. Along with a modest speed ADC, clearly the slower and cheaper sort of RAM will also suffice in a DSO using a CCD input, leading t o a very economically priced instrument wit.h a high perforriiance. On the olher hand, in instruments with ADCs operating at 100 oI even 500Ms/s, you may have been wondering how C'VC'II t h c vcry lasicst, most power-hungry arid expensive RAM could cope. Thc answcr is that it cannot, but that it does no1 have 1.0,siriw the samples are stored in a w r y spccific order - a n d so wc d o not nccd ;I irue randorn awess capabiliiy. This enables (he use oI RAM whose access time is greater than the period of the sampling clock, by using successive parallel banks ol RAM for successive samples as indicated in Figure 7.8. Only the demultiplexer distributing the samples t o the latches has to work at the full rate. Display formats We have now covered most of the techniques used in DSOs to acquire the waveform, what they are used for and how they work. This section looks at the three main methods of presenting the captured waveform on t h c screen. These are the dot display, dot joining (also callcd lincar or pulse interpolation) and sine interpolation. These are iIIustrat.ed in Figure 7.9. Note that if thc dot display is used with ~ o ofew points per cycle of displayed waveform, 'perceptual aliasing' can occur, as illustrated in Figure 7.10. Pulsc i n ~ e r ~ ~ o l a t i(dot o n ,joining) provides a good general-


133

purpose display and can be generally r e c o m m e n d e d . W h e r e the w a v e f o r m u n d e r investigation is k n o w n to be s m o o t h and generally of a sinusoidal shape, sine interpolation provides a good representation with as few as three or even only 2.5 samples per cycle. However, it should not in general be used for pulse waveforms, as here it can introduce ringing on the display w h i c h is not present on the actual w a v e f o r m if the pulse risetime is less t h a n about two or three sample periods, see Figure 7.11. Having m e n t i o n e d perceptual aliasing above, perhaps a w o r d should be said about true aliasing, a l t h o u g h this is really m o r e an u n f o r t u n a t e result of inappropriate control settings on the a c q u i s i t i o n - rather t h a n on the display - process. The topic has already b e e n m e n t i o n e d in Chapter 6, see Figure 6.9 and associated text. A t h e o r e m due to Nyquist states that to define a sine wave, a sampling system m u s t take m o r e t h a n two samples per cycle. It is often stated that at least two samples per cycle are necessary, but this is not quite correct. Exactly two samples per cycle (usually k n o w n as the 'Nyquist rate') suffice if you h a p p e n to k n o w that they coincide with the peaks of the waveform, but not otherwise, since t h e n although you will k n o w the frequency of the sine wave, you have no knowledge of its amplitude. And if the samples h a p p e n to occur at the zero crossings of the waveform, you w o u l d not even k n o w it was there. However, with more t h a n two samples per cycle - in principle 2.1 samples would be fine - the position of the samples relative to the sine wave will gradually drift t h r o u g h all possible phases, so that the peak amplitude will be accurately defined. As we have seen in Figure 7.9, a good sine interpolator can m a n a g e very well w i t h as few as 2.5 samples per cycle, always assuming of course that the w a v e f o r m being acquired is indeed a sine wave. For non-sinusoidal waveforms, a sine interpolator is inappropriate (except in the case of certain i n s t r u m e n t s w h i c h can suitably preprocess the w a v e f o r m before passing it to the sine interpolator). For non-sinusoidal waves, accurate definition of the w a v e f o r m requires that the sampling rate should exceed twice the frequency of the highest h a r m o n i c of significant amplitude. If frequency c o m p o n e n t s at m o r e t h a n half the sampling rate are present, t h e y will appear as 'aliased' frequencies lower t h a n half

134

Oscilloscopes

DIGITIZING RATE IS 25 MHz

INPUT SIGNAL:

SINE INTERPOLATOR

10 MHz

5 MHz


2.5 MHz

I35

1 MHz

Figure 7.9 The display reconstruction type influences the useful storage bandwidth of a digital scope. To trace a recognizable sine wave takes at least 20 and preferably 25 samples/cycle with dot displays. Pulse-interpolator displays produce a useful trace with about 10 vectors per cycle; peak errors make your measurements more difficult w h e n fewer are used. The sine interpolator in the Tek 2430 display shown in the lower series of diagrams reproduces sine waves with only 2.5 samples/cycle, finally approaching the limits that the sampling theory suggests (courtesy Tektronix Inc.)

136

Oscilloscopes

the sampling rate. This will give rise to an inaccurate, misleading r e p r e s e n t a t i o n of the w a v e f o r m . You should always be aware of the possibility of aliasing, for DSOs do not appropriately low-pass filter the input w a v e f o r m to p r e v e n t it. There are several tests you can do to check for the presence of aliasing. First, if the DSO in use has a real-time a n a l o g u e capability, you can use this to observe the w a v e f o r m - if it looks the same as the digitized version all is well. If the scope has no a n a l o g u e capability, check that the shape of the w a v e f o r m does not c h a n g e w h e n you select a higher sampling rate (a faster time/div setting). Some digital m o d e - o n l y DSOs have alias-detect features, w h i c h can be very useful. For example, a DSO m a y feed a sample of the input signal to a f r e q u e n c y counter.

o 0

ooo

9Q

oo

Q

oo o

%

oQ 9 9

9

9o

~

O0

(a)

oo

9

N 9

9 Oo 0

9 ooo

Q

00

9

I 9 oo

9 0

9 o 0

(b) F i g u r e 7.10 Perceplual aliasing errors are so n a m e d because s o m e t i m e s the dot display can be i n t e r p r e t e d as s h o w i n g a signal of l o w e r f r e q u e n c y t h a n the i n p u t signal. But this is not true aliasing. Tile a c t u a l w a v e f o r m is there; y o u r eye - n o t the scope - makes the mistake. Note t h a t in (a) w h a t seems to be m a n y u n t r i g g e r e d sine waves is really o n e w a v e f o r m . W h e n vectors are d r a w n b e t w e e n the points in (b) n o t e t h a t v e c t o r displays can p r e v e n t p e r c e p t u a l distortion b u t can still s h o w peak a l n p l i t u d e errors w h e n data points do not fall on the signal peaks (courtesy Tektronix Inc.)


137

F i g u r e 7.11 Displays constructed with sine interpolation avoid perceptual aliasing and envelope errors w h e n used to display sine waves. But an interpolator designed for good sine wave response can add w h a t appears as pre- and overshooting to the display of a step function w h e n there are fewer than three samples taken on the step. The error is minimized if more than three samples are taken and with n a r r o w spectrum waveforms such as sine waves. The p h o t o g r a p h is a double exposure of a signal with no samples on the step; the first trace is d r a w n with a sine interpolator and the second with a pulse interpolator (courtesy Tektronix Inc.)

If this detects that the frequency is too high relative to the sampling rate (which is d e t e r m i n e d by the selected time/div setting), t h e n a w a r n i n g light m a y be lit, or a w a r n i n g a n n o t a t i o n appear on the screen.

Record length and trace expansion Usually, DSOs display 1000 points across the screen. This is sufficient, w h e n displaying just a few cycles of the input waveform, to present an almost continuous line trace, even with a dot display. Consequently, few DSOs display m o r e t h a n 1000 (or 1024) points across the graticule. In the case of DSOs using an LCD display, of w h i c h several are illustrated, the limited resolution of the current generation of LCD display devices m e a n s that in m a n y such i n s t r u m e n t s only 256 or 512 points in the horizontal direction are provided, or just 32 points in the case of the shirt-pocket oscilloscope of Figure 1.4. Likewise, vertical resolution m a y also be limited, the price paid for a small, lightweight, b a t t e r y - o p e r a t e d i n s t r u m e n t . The n u m b e r of horizontal points displayed, however, is not necessarily the same as the n u m b e r acquired and stored in the

138

Oscilloscopes

display memory. The number of points stored in memory is called the record lcngth. Record lengths or 41< o r 8 K are not u r ~ c c ~ r n m c ~ r ~ ( l . K is sliorthand for 1024 points). This mcans that, cxprcsscd in terms of the display width, 111’ t n 400 per cenl pre- or post-trigger iiilorrnation can be stored, and any part of the frozen record can be displayed on the screen at will. Most DSOs also offer a horizontal post-storagc expansion facility, whcrcby they display less than 1 I< points across the screen, enabling fine detail of the stored waveform t o be examined at will, admittedly at reduced resolution. Similarly, vertical trace expansion is usually offered: clearly the more bits of vertical resolution the DSO provides, the greater the usable degree of vertical expansion. Post-storage expansion is just one of the facilities which set DSOs apart from analogue (tube) storage oscilloscopes: with the latt.er, t.he trace is stored on the screen or storage mesh and cannot be moved in any way after storage. Likewise, DSOs can provide a whole range of signal processing operatioris, both pre- and poststorage, not possible on a n analogue storage scope. Two of these are averaging and smoothing; t l i i arc ~ kuth wavciorrii proccssirig I e ch n iq LIcs lor red u ci n g n oi s c t )n d i sp 1;I)Icd w a vc f o rm s . Signal processing Averaging is used for reducitig noise o i t Inultiple Jcquisitions. Smoothing can also be used with repetitive acquisitions, but it acts on each acquired waveform independently. I t can, therefore, unlike averaging, be used o n a single shot acquisition. Smoothing is a filtering algorithm that avcrages the values of five consecutive points on the waveform, and leaves the result at the centre point. I t then moves 011 one point and repeats the process. Note that the five points averaged a t each successive application of the algorithm are not all ‘raw‘ sample values. The two earliest points are thrmselves smoothed values a n d so were in their turn averaged with even earlier points, as shown in Figurc 7.12. By ’smearing’ five points together, smoothing is vcry effectivc: ar rcdiicing random high-frqucncy noise on. t.h.e display, but as Figure 7.12 shows, it cosls y o ~ ibdndwidth. In this respect, although irnplemen~edi n a n entirely different way, i l is atic7logoits to the smoothing niode of a sampling scope, see


139

smoothed waveform (partial) C'

section of waveform record, acquired single shot

1.1.I.I.I.1.I.1.1 A

B

C

D

one smoothing set yields: C' -

(a)

the next smoothing set yields: D' =

E F A'+B'+C+D+E 5 B'+C'+D+E+F

smoothing algorithm

Yn = N

i=1

Yn-i + "= i~0 Xn+i

//~\

ii

where

N

M

n

Yn Xn

is the set of points processed; in this case, N = 5 (two points on either side of the centre point). is the number of points used on each side of the centre point, that is (N-1)1/2; in this case M = 2. is the horizontal position, represented by a point in the record (0 to 1023). is the vertical value (result); the output array is the acquired value; the input array.

I

/ \ \

\

ii

/ \ \

\ I

I

before smoothing

~ " 6 ~ O.. f

It" "4 ~ ...O, . ~ " h " "Q..~

after smoothing

(c)

Figure 7.12 Waveform processing. In (a) smoothing moves through a waveform record, point by point. It averages each point with the two points behind and the two points ahead. It then leaves the averaged result at the centre point. As this figure shows, the first two values in each five-point average come from previously processed points. Smoothing under the worst-case sample-rate conditions shown in (c) reduces the triangle wave to a nearly straight line (courtesy Tektronix Inc.)

140

Oscilloscopes

Chapter 6. And in exactly the same way, the reduction in bandwidth can be prevented from affecting the wanted waveform by sufficiently increasing the number of sample points per cycle of the waveform. Averaging differs from smoothing in that the points averaged all occur at exactly the same point on the waveform at each rcprtition. Thereforc rherc is n o reduction in bandwidth and the improvement in signal-to-noise ratio is independent of the frequency of the nuise (withiri certain lirnils). During any triggcrcd acquisition, a particular sample’s arnplitude has two parts: a signal co~~iporicrit arid a ~ioisccornporicnt. Becausc the incoming signal has a fixed relationship 1.0 the trigger point, thc signal-component’s amplitude rcmains the same from uric repetitive-waveforrri acquisiliun l o Ihe next. Random noise, on the other hand, has 110 lixed time relationship with the trigger point. The noise contribution to a particular sample’s amplitude may be positive o n one acquisition and negative on another, with an average of zero in the long run. Thus the greater the number of acquisitions averaged, the greater the noise reduction. The number o f acquisitions averaged is usually user-selectable in powers of two from 2 to 256. However, you would not want to wait for 256 acquisitions to take place before the waveform could be displayed, so instead of the usual sort of average, a running average over IZ sarnplcs is used. Two different sorts o f running avrragr are used, exponentid avcraging and stable avcraging. Thc formcr works as follows suppose wr s r l c c ~svrraging w t l r 17 = 16 acquisitions: then the value of each sample actually displayed is calculated as 1/16th 01 thc saniple ,just taken plus 15/161hs the corrcsponding sample displuyed ( n o t t a k e n ) o r 1 I ~ Cprt‘vious xquisiliori. Thus any aberration from thc. true valuc of t h e signal due to noise on the sample will be reduced by a factor of 16. Thc currently displayed value is niaiiily dererir~inedby ~ hlast r n samples, where M equals 16 in the example just given. Since, with the arrival of a new sample, the value of the current sample is reduced t o 15/16ths before adding 1/16th of the new sample, after 16 new samples it will be reduced to ( 1 5 / 1 6 ) ” or 38 per cent. Now this is (approximately) e-‘, i.e. the effect of samples taken fades out

Digital storage oscilloscopes 141 exponentially with time over n samples, hence the n a m e exponential averaging. If there is a sudden change in the input waveform itself, for example if the Y volts/div or the X time/div setting is changed, then the effect of this will be registered on the display in due course, subject to a time constant determined by the selected value of n. The resultant delay could be m a n y seconds, so some DSOs are designed to switch temporarily to stable averaging immediately following a change in any control setting which affects the display, switching back again after n acquisitions. Stable averaging weights succeeding samples less and less heavily, i.e. the earlier samples have most effect, unlike the equal weighting of exponential averaging. The first sample is displayed as is. The second displayed point i s t h e second acquired point averaged with the first one. The next point is displayed as the average of the first three and so on, until at the nth point, exponential averaging is resumed. Thus the display rapidly converges to the n e w picture. The effectiveness of averaging in reducing noise is clearly illustrated in Figure 7.13. Averaging not only decreases noise, it can actually increase the resolution of a DSO, at least for repetitive signals. Stable averaging increases the digitizer's potential resolution by a factor of n, or log2 n bits, w h e n n acquisitions are averaged. Exponential averaging provides the same improvement, but only after rather more acquisitions. Paradoxically, it is only the presence of the very noise on the signal which averaging is used to reduce, which provides the increased resolution, as a m o m e n t ' s reflection will show. For in an ideal noise-free system, any given voltage within the input range of the ADC will always be digitized as the same value. Thus for an ideal 8-bit ADC, a constant mid-range voltage which digitizes as 123 will always digitize as 123, even t h o u g h its actual value is a n y w h e r e b e t w e e n voltages corresponding to i22.5 and 123.5. Now imagine, however, that there is just one digit peak to peak of r a n d o m noise riding on the signal. An input voltage which ideally should digitize as 123 will still do so on average. However, an input which should ideally digitize as 122.5 will n o w digitize as 122 as often as 123. So if we add sixteen successive samples and divide the answer by 16, the odds are

142

Oscilloscopes

Figure 7.13 These photographs show how averaging cleans up the display of a spike that is nearly completely obscured by noise (courtesy Tektronix Inc.)

(statistically) t h a t w e will g e t

122.5, w h i c h

e x a c t l y as a 9-bit r e s u l t . F u r t h e r m o r e ,

we can represent

a level w h i c h should, in an

ideal s y s t e m , digitize as 1 2 2 . 7 5 will o n a v e r a g e digitize as 123 t h r e e t i m e s as o f t e n as 122. W e c a n r e p r e s e n t this e x a c t l y as a 10-bit r e s u l t .


143

Due to the statistical nature of noise, the signal-to-noise ratio improves w i t h increasing n rather more slowly t h a n the potential increase in resolution. T h e signal-to-noise i m p r o v e m e n t is just 3 dB per doubling of the n u m b e r of averaged samples n, i.e. the effective n u m b e r of extra bits is 1/2 log2 (n) or 4 bits for 256 samples. Bearing in m i n d the r e q u i r e m e n t for 1-bit peak-to-peak of noise (1-bit loss of accuracy) to make it all happen, 256 samples can improve the resolution of an 8-bit system to ( 8 - 1 + 4) = 11 bits. With less t h a n 1 bit of noise the i m p r o v e m e n t will not be obtained, while with m o r e t h a n 1 bit of noise, more t h a n 256 samples will be required in order to drive the higher level of noise d o w n as far. Special features of D S O s In this final section we look at some uniquely useful features of DSOs, h o w they w o r k and h o w they are used. First, you m a y recall from the introductory section that digital-mode-only scopes often use a bit-mapped display. This implies that m o r e t h a n one sample value could be stored at any horizontal distance across the screen, corresponding to any u n i q u e m o m e n t in the scan. This m e a n s that, with a triggered repetitive scan, every value of the input voltage ever recorded at each point on the w a v e f o r m can be displayed on the screen. Now, of course, with an ideal noise-free w a v e f o r m stably triggered, each point on the w a v e f o r m will be converted to the same sample value on every scan - but t h e n life is not ideal, is it? Hence the usefulness of this 'infinite persistence' mode, w h i c h is more eloquently illustrated by Figure 7.14 t h a n by words. In oscilloscopes with both a digital storage and a real-time analogue capability, a conventional electrostatic deflection oscilloscope c.r.t, such as that described in Chapter 9 is used. In such DSOs, a bit-mapped display is not appropriate and a m o r e economical m e m o r y can be used. This usually has just one (sometimes two) storage location per point in the record, for each trace. Normally, the value recorded for the current sample is stored in the appropriate location on each repetitive scan. However, if the i n s t r u m e n t offers an envelope mode display, t h e n the sampling can, w h e n required, be organized s o m e w h a t

144 Oscilloscopes

~i~

....~i~.~.: . . . . .

.." '~ "~~%r .....~

~

~,~

,~.-i~~?":~~:~

9

,,, ::~,,

~

:N

~~

j

k

Figure 7.14 'Digital Phosphor Oscilloscopes' display, store and analyse complex signals in real time, using the three dimensions of signal information: amplitude, time and distribution of amplitude over time, as in this display of an eye diagram on a TDS794D oscilloscope (courtesy Tektronix Lid)

differently. In e n v e l o p e m o d e , alternate screen locations are used to store the highest value digitized to date (say odd locations), while in t h e o t h e r locations, the lowest value is similarly stored. The stored w a v e f o r m is displayed in dot-joining m o d e , a n d again with an ideal noise-free w a v e f o r m with no f r e q u e n c y c o m p o nents a b o v e half the s a m p l i n g rate, the display will look the same as w i t h o u t the e n v e l o p e m o d e in use. However, if the w a v e f o r m is u n s t a b l e as in the p r e v i o u s e x a m p l e , or if t h e r e are c o m p o n e n t s a b o v e the Nyquist rate, t h e n the picture can look quite different, see Figure 7.15. In the middle photo, the h i g h - f r e q u e n c y carrier is incorrectly s h o w n as aliased to only 20 times the m o d u l a t i o n frequency, in this single shot picture. In successive acquisitions, the sample points w()uld fall at different points on the carrier ( a s s u m i n g it was not a locked h a r m o n i c of the m o d u l a t i o n f r e q u e n c y ) , giving c o n s t a n t l y c h a n g i n g pictures, each very similar to that s h o w n .


145

ENVELOPE MODE

Figure 7.15 These photos are of an amplitude modulated signal as it was displayed by a non-storage scope, by a digital storage scope in normal mode and by a digital storage scope using the envelope mode. The modulating frequency is reproduced easily in both digital acquisitions. The carrier, however, is being digitized at a rate m u c h less than two samples per period and is shown as a lower frequency in the middle photograph. The envelope mode used as an anti-aliasing feature results in a display very m u c h like the non-storage signal (courtesy Tektronix Inc.)

146 Oscilloscopes In t h e e n v e l o p e m o d e display, l o w e r p h o t o , t h e m a x i m u m a n d m i n i m u m values at a l t e r n a t e positions in the X direction are j o i n e d by vectors, giving a display very similar to the n o n - s t o r a g e display, top p h o t o . W i t h the usual d e n s i t y of 100 dots per h o r i z o n t a l graticule division, the result is a b a n d of light indicating the e n v e l o p e of the m a x i m u m a n d m i n i m u m values e n c o u n t e r e d . The e n v e l o p e m o d e leads us into o n e of t h e m o s t i m p o r t a n t f e a t u r e s of t h e DSO: glitch c a p t u r e . A glitch is a r o g u e n a r r o w pulse w h i c h can play haw~c in digital systems. It is typically d u e to a rare c o n d i t i o n a n d d e p e n d i n g on the p r e v i o u s pulse s e q u e n c e , m a y only a p p e a r o c c a s i o n a l l y often w i t h dire r e s u l t s - m a k i n g it very difficult to observe. If the triggered w a v e f o r m is a c q u i r e d repetitively for a long p e r i o d in e n v e l o p e m o d e , t h e n w i t h luck the glitch, w h e n it occurs, will be c a u g h t as an isolated positive level s a m p l e s t a n d i n g up f r o m the

Figure 7.16 The M221, Inch1 Amplicon, is a gc)od cxalnplc c)f the burgeoning market ill plug-in inslruments tc~ fil in tile IBM PC or compatible personal c~mpu/ers. It tcalures a maximum sampling rate of 20Ms/s on each of its two input channels simultaneously, each with 8 bit resolution (courtesy Amplicon Liveline Ltd)

Digital storage oscilloscopes 147

Figure 7.17 Many high bandwidth digital storage oscilloscopes, at fast timebase settings, use repetitive sampling (equivalent time) techniques to digitize signals. The LeCroy model LC684DXL features 2 Gsamples/second samplers for each of its four channels. Thus two channels may be sampled at 4 Gs/s, while single channel operation at 8Gs/s provides a 1.5 GHz single shot bandwidth (courtesy LeCroy Ltd)

logic 0 level, or as a n e g a t i v e - g o i n g glitch f r o m the i level. H o w e v e r , if the t i m e / d i v setting is, say, 10 ~s/div, t h e n w i t h 100 points per division, a glitch of w i d t h less t h a n 100 ns could v e r y easily be missed. A p o w e r f u l e n h a n c e m e n t of e n v e l o p e m o d e for digital glitch c a p t u r e is to r u n the ADC s a m p l e r at its m a x i m u m rate regardless of the t i m e / d i v setting. Thus in the e x a m p l e just given, the s a m p l i n g rate w o u l d n o t be 10 Ms/s (100 samples p e r 10 b~s), but, say, 50, 100 or m o r e Ms/s, w h a t e v e r t h e scope's m a x i m u m rate is. H o w e v e r , only o n e s a m p l e v a l u e (the h i g h e s t or lowest in a n e v e n or o d d screen location respectively) is r e c o r d e d p e r 100 ns sample period. By r u n n i n g the digitizer at its m a x i m u m rate in e n v e l o p e m o d e , regardless of the t i m e / d i v setting, the o p t i m u m digital glitch c a p t u r e p e r f o r m a n c e is always obtained. The DSO can t h e r e f o r e be left 'babysitting', just w a i t i n g for a glitch to occur, w i t h a h i g h probability t h a t it will be

148 Oscilloscopes c a p t u r e d provided that it is not so n a r r o w that it can slip b e t w e e n samples at the i n s t r u m e n t ' s m a x i m u m digitizing rate. In high speed logic circuitry, notably ECL logic, glitches as n a r r o w as one or two n a n o s e c o n d s can occur. Even on one of the m o r e expensive DSOs capable of digitizing at 500Ms/s, the digital glitch capture m o d e described above could not g u a r a n t e e to capture that, let alone an oscilloscope with a 1 0 0 M s / s m a x i m u m digitizing rate. However, there is a n o t h e r approach, using a n a l o g u e peak detectors. These are incorporated in the Tektronix 2430, with its 1 5 0 M H z a n a l o g u e m o d e b a n d w i d t h and 100 Ms/s digital mode, enabling it to capture a 2 ns spike at any s w e e p speed. Inevitably, due to pressure of space, special facilities f o u n d in some DSOs have not b e e n covered, while some of the finer points of the m o d e s w h i c h have been covered have b e e n glossed over. However, e n o u g h has been said to convey the message that choosing a DSO is a m o r e complex task t h a n choosing an a n a l o g u e scope. Do not rely on the assurances of the salespeople - having m a d e a tentative choice of an instrum e n t to m e e t a particular m e a s u r e m e n t need, you should insist on a d e m o n s t r a t i o n of its ability to fit that particular application. If the i n s t r u m e n t is for general laboratory use rather t h a n a particular application, there is no substitute for close scrutiny of the specifications including the small print. For a generalpurpose i n s t r u m e n t , m y personal preference would always be for one with a real-time a n a l o g u e scope capability as well as digital storage.

8

Oscilloscopes for special purposes It would be very difficult, indeed quite impossible, to design an oscilloscope suitable for all the very wide range of uses to which this most versatile of electronic instruments is put. Consequently there is and always will be a wide variety of oscilloscopes, each aimed primarily at its o w n particular field of application. Of course a mainframe plus plug-in approach permits one oscilloscope (plus a cupboard full of plug-ins) to cover a wide variety of uses, but this format is confined to m e d i u m and large oscilloscopes. The mainframe will be either an analogue-only scope, or offer storage facilities, n o w a d a y s invariably digital storage as manufacturers no longer offer oscilloscopes using the type of storage tube described in Chapter 11. A non-storage scope m a y be cheaper t h a n a DSO of comparable single shot bandwidth, t h o u g h the price differential is decreasing steadily. But first let us consider the smaller, simpler, specialized instruments. Small portable scopes Being such versatile instruments, oscilloscopes often get used in inaccessible places, d o w n a hole in the ground, for example, or at the top of a pole. Here, a small, light instrument, p o w e r e d from internal batteries, has obvious advantages. Figures 8.1 to 8.4 show a selection of such instruments, some p o w e r e d from internal primary ('dry') batteries and some from internal secondary (rechargeable) batteries. Often the latter variety incorporates a m a i n s - p o w e r e d battery charger, and depending on the make and model it may also be possible w h e n mains is available to use the oscilloscope whilst simultaneously recharging the battery for later portable use. Figure 8.5 shows a n o t h e r eminently portable oscilloscope, the Fluke 'ScopeMeter'| model 123 with a 20 MHz bandwidth. The i n s t r u m e n t also doubles as a dual input recorder, and as two 5000 counts true-rms digital multimeters. An optically isolated RS-232

150 Oscilloscopes

Figure 8.1 Tile Hitachi V-209 20MHz dual trace portable oscilloscope operates fronl its internal battery pack, external 12 V d.c. or 90-260 V a.c. mains supply (courtesy Thurlby-Thandar Lid)

interface is p r o v i d e d , a n d t h e i n s t r u m e n t is safety certified to 600 V CAT III level. A line p o w e r e d a d a p t e r / b a t t e r y c h a r g e r is i n c l u d e d , b u t - w h i l e w e i g h i n g in at just 1.2 k g - t h e m o d e l 123 p r o v i d e s 5 h o u r s ' p o r t a b l e m a i n s - f r e e o p e r a t i o n f r o m its i n t e r n a l NiCad batteries. O t h e r m o d e l s in t h e r a n g e i n c l u d e the ScopeM e t e r @ 199, w i t h t w o i n p u t c h a n n e l s each h a v i n g a m a x i m u m digitizing rate of 2.5 Gs/s. This p r o v i d e s a 2 0 0 M H z b a n d w i d t h w i t h o u t resort to sine i n t e r p o l a t i o n . For less d e m a n d i n g applications, t h e r a n g e also i n c l u d e s 100 MHz a n d 60 M H z models.

Oscilloscopes for special purposes

151

Figure 8.2 The ADC200 is a PC-based 'virtual oscilloscope', connecting to the host personal computer via a parallel port. A different port (LPT2, say) from the printer's LPT1 is a good idea. Advanced trigger modes, such as 'save to disk on trigger, with time and date stamp', help track down intermittent faults. Three models, with m a x i m u m sampling rates of 20, 50 and 100Ms/s, are available: all provide 8 bit resolution. (Reproduced by courtesy of pico Technology Ltd)

Educational scopes There is one category of oscilloscope, however, w h e r e high performance is not so important a consideration. M u c h more important in a scope for the educational market are simplicity of operation, low cost and, above all, safety. Few oscilloscope manufacturers specifically address this market, being content with the hope (often forlorn) that the lowest price model in their range will pick up some educational sales. One of the few manufacturers with a product truly designed from the g r o u n d up for this particular market is Metrix. Figure 2.3 shows their model OX71 'Didascope', so n a m e d from its didactic connotations. From the point of view of the parameters most important in a highperformance scope, its specification is very m o d e s t - just a single channel with 5 MHz b a n d w i d t h at a highest sensitivity of 50 mV/ division. However, in view of its intended sphere of operation, it is double insulated (making it suitable for floating m e a s u r e m e n t s ) and meets safety specification EN61010 (IEC 1010-1 ), class II. For ease of operation, automatic triggering is available and the instrument even offers XY operation and Z modulation.

152

Oscilloscopes

Long-persistence scopes Traditionally, an i m p o r t a n t category of special-purpose oscilloscopes was that used for displaying l o w - f r e q u e n c y repetitive waveforms, or fast single shot events. With the m e d i u m / s h o r t persistence p h o s p h o r s such as P31 used in the majority of oscilloscopes, flicker of the trace will be noticed w h e n its repetition rate is m u c h lower t h a n 50 times per second. The lower the repetition, the worse the flicker, and at a b o u t 15 traces per second the eye ceases to see a trace at all, seeing only a moving spot of light bobbing up and d o w n . One solution to this p r o b l e m is to use an oscilloscope fitted w i t h a c.r.t, having a long-persistence phosphor. With this type,

Figure 8.3 The notebook type VC-5430 portable oscilloscope runs from internal batteries, dedicated a.c. power adaptor or external battery pack. Its two 30Ms/s input channels each provide a 50 MHz bandwidth, with timebase speeds down to 5 ns/div. The instrument's most unusual feature is a backlit colour-TFT liquid crystal display, adding clarity to multi-trace displays (courtesy Hitachi Denshi (UK) Ltd)


153

Figure 8.4 The battery operated hand-held THS730A oscilloscope, with its 1 Gs/s samplers, provides a 200 MHz bandwidth on each of its two input channels. Cursors ease measurements, while the various trigger modes include, for TV work, odd field, even field and line (courtesy Tektronix UK Ltd)

t h e p a t h t r a c e d o u t b y t h e spot c o n t i n u e s to g l o w for s e v e r a l or e v e n m a n y s e c o n d s after its passage. T h e r e is a w i d e r a n g e of p h o s p h o r s available to t h e c.r.t, m a n u f a c t u r e r , see A p p e n d i x 1, b u t o n e of t h e c o m m o n e s t l o n g - p e r s i s t e n c e p h o s p h o r s is t y p e P7, w i t h a b l u e 'flash' ( f l u o r e s c e n c e ) a n d a y e l l o w i s h - g r e e n a f t e r g l o w ( p h o s p h o r e s c e n c e ) w h i c h fades o u t g r a d u a l l y o v e r a b o u t e i g h t seconds. A d e e p y e l l o w filter glass in f r o n t of t h e c.r.t, s u p p r e s s e s t h e spot, w h i c h c o u l d o t h e r w i s e be d i s t r a c t i n g as it is q u i t e bright,

154 Oscilloscopes

Figure 8.5 Tile Fluke 123 Industrial ScopeMeter| samples al up to 25Ms/s (1.25Gs/s in equivalent time), providing a bandwidth of 20MHz. Features include a t r u e r.m.s, digital multimeler t ' u n c t i o n , a n optically coupled RS232 port and up to five h~urs' ballery life (reproduced by courtesy ~t' Fluke Europe BV)

leaving o n l y t h e a f t e r g l o w visible. With a l o n g - p e r s i s t e n c e scope using this p h ~ s p h o r , r e p e t i t i o n rates d o w n to a b o u t o n e trace per s e c o n d or less can be c o m f o r t a b l y v i e w e d : t h e m o v i n g spot of light is visible, but leaves its p a t h traced o u t as a line b e h i n d it. Such an i n s t r u m e n t also allows the o b s e r v a t i o n of short, single o c c u r r e n c e s . For e x a m p l e , t h e few milliseconds of contact b o u n c e on a switch or relay can be 'fr~zen' using single sh~! triggering, a n d o b s e r v e d for a few s e c o n d s until the trace fades away. T h e r e w e r e t w o d i s a d v a n t a g e s to t h e l o n g - p e r s i s t e n c e scope, useful t h o u g h it u n d o u b t e d l y was in a p p r o p r i a t e c i r c u m s t a n c e s .


155

The first is that the trace persists for a few seconds only, and is t h e n gradually irretrievably lost (though it can of course be p h o t o g r a p h e d in the meantime). The second is that if the timebase runs repetitively but w i t h o u t being correctly triggered, the screen rapidly fills up with a spaghetti jungle of u n w a n t e d traces that always seem to take ages to fade away. Although long-persistence scopes were c o m m o n l y available at one time, few if any manufacturers n o w offer the option of a c.r.t. with a long-persistence screen in one of their standard scopes. In the past, a long-persistence scope offered a m u c h cheaper solution to m a n y m e a s u r e m e n t problems t h a n the t h e n only alternative - a storage scope using one of the storage tubes described in Chapter 11. But the function of both these types has n o w been taken over by the ubiquitous digital storage oscilloscope.

Recording oscilloscopes An alternative to p h o t o g r a p h i n g the trace on the screen of a long-persistence scope or a storage scope is to record it on paper. Once u p o n a time this was done with tracing paper held against the graticule of the c.r.t., a pencil and a steady hand. Nowadays there are oscilloscopes with built-in recorders capable of plotting out the trace s h o w n on the screen. Figure 8.7 shows such an i n s t r u m e n t - the chart paper outlet is visible on the left side of the top of the instrument, and can be seen in operation in a n o t h e r i n s t r u m e n t from the range in Figure 8.6. Usually, as here, the 'hardcopy printout' can be fully a n n o t a t e d with the graticule and the instrument's settings, a great convenience and time saving. The recorder need not be built in. With m a n y DSOs, a conventional XY recorder or YT (chart) recorder can be pressed into service. In this case, the sequence of digital values representing the trace is passed to a DAC (digital-to-analogue converter) w h i c h reconverts it to a time-varying voltage, similar to the original signal but suitably slowed d o w n for the benefit of the XY recorder. This signal is connected to the recorder's Y input while an appropriate ramp voltage, representing the original timebase, is fed to the recorder's X input. Both X and Y waveforms are fed out simultaneously, w h e n the appropriate button, labelled

136

Oscilloscopes

Figure 8.6 The DataSYS 7100 is a good example of oscilloscopes for special purposes, in [his case, mains power analysis. Measures V, I, W, VA and PF with simultaneus display of Voltage, Curren[ and Power waveforms. The instrument performs specific iesls, such as checking cquipmenis [o EN61000-3-2 (Current Harmonics), equivalent to IEC 1000-3-2, and alsc> dubles as a powerful generalpurpose 200 MHz digital si~>rage oscillosccipe (reproduced by courtesy of Gould Nicolet Tcchn1000 wavcliiriii digilizcr. displa>ing a n ESU pulse with a 500 ps risetime o i i i t \ iiptional display u n i t . This instrurnciil tiad a rnaximum realtiiiie digitizing [rare ( 1 1 i i p IO 200 Gs/s, aiiti pi-ovirlcd a l?aiidwidtli i i L I00OMHz with a 350 ps r~sctirnc tor capturing transient single shot signals. The cornpanion SCDSOO has a 5 0 0 0 M H z bandwidth a n d a n 801's rkcliiiie. Though now disciintinued, rhcy arc widely used in particle physics, ato[iiic- I a h , ctc. (courtesy Tcktronix UI< Ltd)


I75

Figure 8.22 The MS4623B Vector Network Measurement System is shown displaying the conjugate filter response of a band separation diplexer, made possible by the instrument's third measurement port. The instrument covers 10 MHz-6 GHz and the range includes economical two port single path reflection/ transmission analysers with ranges to 3 GHz and 6 GHz max. (reproduced by courtesy of Anritsu Ltd)

a risetime of less than 80 ps. At the 5ps/point horizontal setting, both models operate at a true 200 G s a m p l e s / s e c o n d rate. This sort of performance never came cheap, and both m o d e l s are n o w discontinued, but continue to be essential tools in the more advanced (and secretive) high energy physics laboratories.

9

How oscilloscopes work (1): the carat. Many logic analysers and some DSOs use magnetically dellecled c.r.t.s either monochrome or coiour. This is the type of display technology used in TV scts. The operation of TV type rubes is well covrred i n ol.her volurnes in t.he Newnes series, 10 which the reader is rufcrrud for further information. In c.r.t. storagr oscilloscopes, h e cathode ray tube is basically similar to the electrostatically deflected type of tube described in this chapter, but with a special screen or the addition of one or more storage mcshcs: storage tubes arc dcscribcd in Chapter 1 1 . This chapter deals solely with the high-performance c.r.t.s using electrostatic deflection, used in non-storage oscilloscopes. Such an oscilloscope may also include a digital storage capability, as in Figure 1.5, a n d the same c.r.t. is then used for both the conventional reaI-time display and for the storage mode display. The cathode ray tube is the main component of an oscilloscope. A cathode ray tube consists basically o f a n electrode assembly mounted in a n evacuated glass vessel (Figure 9.1 ) . The electrodes perform t tic following functions: 0 A

triode assembly geiieratcs the electron beam, originalIy

callccl thrb'cathode, ray'. J t consists of a cathodc I< heated by a filament F, a control grid G a n d ilic first beam-accclcrarion elcc.1rod(: ( 1 ). 0 A n clcctrodc ( 2 ) focuscs the beam. 0 The k a i r i is IIirii f u r i l l t a r ac.c.clcraIrd before r v ~ c h i n gLhr 0

deflection plates. 'l'hc~vertical deflection plates change the direction of the beam in proportion 10 the potential difference between them. When this is zero. i.c. the two p1atc.s arc at t h e same potential, the beam passes through undeflectcd. The vertical deflection plates are s o called because they can deflect the beam in the vertical direction, so that it hits the screen at a higher or a

How oscilloscopes work (1)" the c.r.t. gun /---------~ 1E)

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lower point; they are actually m o u n t e d horizontally above and below the beam, as s h o w n in Figure 9.1. Similarly the horizontal deflection plates permit the b e a m to be deflected to left or to right. 9 The deflected b e a m t h e n hits the fluorescent coating on the inner surface of the glass screen of the c.r.t. The coating consists of a thin layer of 'phosphor', a preparation of very fine crystals of metallic salts deposited on the glass. Further details of phosphors are given in Appendix 1. The 'spot' or point of impact of the b e a m glows, emitting light in all directions including forwards. M o d e r n c.r.t.s are aluminized, i.e. a thin layer of a l u m i n i u m is evaporated on to the rear of the coated screen. The electrons pass t h r o u g h this w i t h little retardation, causing the p h o s p h o r to glow as before, but n o w the light emitted rearwards is reflected forwards, almost doubling the useful light output. The potential at the focus electrode is adjusted to obtain a very small r o u n d spot on the end of the tube. Unfortunately, if no other control were provided, it w o u l d often be found that the focus control setting for m i n i m u m spot w i d t h was different from that for m i n i m u m spot height. This is avoided by providing an astigmatism control. In the case of a simple cathode ray tube this consists of a

178 Oscilloscopes p o t e n t i o m e t e r that adjusts the voltage on the final a n o d e a n d screen relative to the deflection plate voltages. Alternate adjustm e n t s of the focus a n d astigmatism controls t h e n p e r m i t the smallest possible spot size to be achieved. With m o r e complicated tubes using a high 'post-deflection acceleration ratio' a n o t h e r electrode is often n e e d e d . This is a ' g e o m e t r y ' electrode a n d is c o n n e c t e d to a n o t h e r preset p o t e n t i o m e t e r , w h i c h is adjusted for m i n i m u m ' p i n c u s h i o n ' or 'barrel' distortion of the display. W h e n an electron b e a m passes b e t w e e n t w o horizontal plates that h a v e a potential difference of V volts b e t w e e n t h e m (Figure 9.2) it is deflected vertically by an a m o u n t :

bYwhere

KVLD 2 Va d L - length of the plates D = distance b e t w e e n the plates and the point on the axis w h e r e the deflection is m e a s u r e d d = distance b e t w e e n the plates Va = acceleration voltage applied tr the b e a m at the level of the plates K = a c(~nstant relating tile charge ~t' all electron to its 111ass

The Y deflection sensitivity r c.r.t, is defined by A Y/V a n d is expressed in cm/V. H()wever, in practice tile inverse relationship

r-j

Figure 9.2 Y-deflection sensitivity - see text (courtesy Enerlec Instrumentation Ltd)

How oscilloscopes w o r k (i): the c.r.t.

179

is normally used: V/AY, in V/cm, i.e. the differential deflectionplate voltage necessary to achieve a spot deflection of 1 cm. Brilliance or intensity modulation (also called Z modulation) is obtained by the action of a potential applied to the cathode or grid that controls the intensity of the beam. Generally, a change of 5 V will produce a noticeable change of brightness, while a swing of about 50 V will extinguish a m a x i m u m - i n t e n s i t y trace. The beam is normally extinguished during 'flyback' or 'retrace'; see Chapter 10. This m a y alternatively be achieved in some c.r.t.s by means of an auxiliary 'blanking' electrode, which can deflect the beam so that it no longer passes t h r o u g h the deflection plates and hence does not reach the screen. Tube sensitivity The deflection plates of a c.r.t, are connected to amplifiers, which can be of relatively simple design w h e n the required output amplitude is low; it is therefore desirable for the tube sensitivity to be as high as possible. To enable the amplifier to have a wide bandwidth, the capacity b e t w e e n the plates must be kept low, so they must be small and well separated. On the other hand, in order to obtain a suitably clear trace of a signal with low repetition frequency (or single shot) the energy of the b e a m must be high. But the ideal tube must be: 9 Short (not cumbersome): D small 9 Bright (high acceleration voltage): Va large 9 And with low deflection-plate capacity: L small, d large This gives a tube with very low sensitivity, considering the formulae: AY Sensitivity -

KLD m

V

2Vad

The requirements for high sensitivity contradict the terms of the equation. Practical cathode ray tubes are therefore the result of a compromise. However, techniques have been developed to improve a selected parameter w i t h o u t prejudice to the others.

180 Oscilloscupcs

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Figure 9.3 Single-\tagc post-dellection acceleration (courtesy Enrrtec Instrurnenration Ltd >

Post-deflection acceleration (p.d.a.) is one of these; see Figure 9.3. To improve the trace brightness while retaining good sensitivity. i t i s arrangrd that the beam passes rhrorigh t.he deflection system in a low energy condition (rclarivcly low initial acccl.oration j; ~~o~t-~dci'lectior~ acceleration is 1 1 1 e r i applied to h e electrons. This is achieved by applying d voltage of several kilovolts t o t h c sci-ccn (11 thch c.r.1. Spiral p.d.a., Figttrc 9.4, is a dcvclopiIicnt ot ~ h cbasic p.d.a. technique, a n d consists of the application of thr p.d.a. voltage to a resistive spiral (of resistance a b o u t 500 MI)) dcposircd on the inner tube surface between the screeri arid the dcf'lccriori sysrern. The unilorrnity o l i h e electric f'ield is improved, which reduces

How oscilloscopes work (1)" the c.r.t. 181 distortion. In addition the effect of the p.d.a, field b e t w e e n the deflection plates is weaker, so the loss in sensitivity caused by this field is reduced. The use of a field g r i d - Figure 9.5(a) - avoids a n y r e d u c t i o n in sensitivity caused by the effect of the post-deflection acceleration field. A screen is i n t e r p o s e d b e t w e e n the deflection s y s t e m a n d the p.d.a.; this m a k e s the tube sensitivity i n d e p e n d e n t of the p.d.a., a significant benefit. The screen must, of course, be t r a n s p a r e n t to the electrons a n d is f o r m e d f r o m a very fine metallic grid. With this s y s t e m w e reach the d o m a i n of m o d e r n cathode ray tubes. The n e x t d e v e l o p m e n t is the electrostatic e x p a n s i o n lens Figure 9.5(b). By modifying the shape of the field grid (e.g. a c o n v e x grid) it is possible to create, w i t h respect to the o t h e r

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182

Oscillosctrpes

electrodes, a n electric field that acts on the electron beam in the same way as a lens acts on a light beam. It is therefore possible to increase the beam deflection angle, for example by a factor of two, which improves the sensitivity by the same amount. The field can also be formed by quadripolar lenses. So, for example, if the sensitivity of a spiral tube is 30 Vlcm in the X axis and 10V/cm in the Y axis, then t he sensitivity of a lens-fitted tube, for the same trace brightness, may be 8V/cm in X and 2 V/cm in Y or even better. To improve the sensitivity b y modifying the deflection system it is necessary t.o d o one of two t.hings: 0

Rrduce t.he distance hetween the plates, iticrcasing thc capacity bctwccn them; in addition i t must be possihlr ti) deflect the beam without it striking them. Lcngtl-icn thc plates, again increasing the capacity; however, the transit t.imt. involved limits the application of this idea.

The transit time is the time taken for an electron to pass through the deflection system: t, = L/electron speed. Suppose that a sinusoidal voltage o f period t,, is applied t o the deflection plates. An electron leaving the plates will be in the same position as one entering the system, because the instantaneous value of the voltage applied to the plates will be the same (one period between the input and the output) and there will be no deflection. To enable the beam to be deflected so a s to trace the outline o f the applied signal, the length of the plates must be small compared with the distance the electrons travel during the period of one cycle o f the signal. So for high-frequency work the plates must he short, which again rc4iices the sensitivity. The prohlcm can he circurnvcntcd by the use of sectional plates (Figiirrt: 7.h).To inipi-ovc rhc scnsilivity scvcral platcs arc placcd in series, conncctcd by rl delay litie. As tlic I)t-opagatiori v r l w i t y of the line is iiiacle q u a 1 to the speed of the electrons in the beam, the devia~ionaccuniulatcs succcssivcly. On thc other hand thc parasitic capacitancc of the platrs is incorporated in the delay line, which must be terminated in its characteristic impedance. The design of the line is entirely determined by its stray

How oscilloscopes work (1): the c.r.t. 183 l

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capacitance a n d the p r o p a g a t i o n time. This brings us to delay-line deflection plates (Figure 9.7). Here, the d i m e n s i o n s of the plates h a v e b e e n r e d u c e d a n d their n u m b e r increased. Two flattened helices are used, each t u r n acting as a deflection plate. The helix is c o n s t r u c t e d in such a w a y that its p r o p a g a t i o n velocity corresponds to the speed of the electron b e a m . These deflection systems, t o g e t h e r w i t h field grids or q u a d r i p o l a r lenses (or both), p e r m i t the c o n s t r u c t i o n of very h i g h - p e r f o r m a n c e tubes. Other tube characteristics

To be suitable for use at high frequencies a c.r.t, must, as already discussed, h a v e a highly d e v e l o p e d deflection system. But this alone is not sufficient w h e n it is r e q u i r e d to observe a n d p h o t o g r a p h fast pulses w i t h low repetition rate or single shot p h e n o m e n a . The brilliance of the display m u s t also be a d e q u a t e . This is w h y 'writing speed' is a n i m p o r t a n t feature in these conditions. Writing speed is defined as the m a x i m u m speed at w h i c h a spot, passing once across the tube face, can be

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184

Oscilloscopes

p h o t o g r a p h e d u n d e r specified conditions (camera, aperture, image/object, film sensitivity). On the occasions w h e n it is necessary to c o m p a r e several fast, single shot p h e n o m e n a occurring simultaneously, the only solution is to use an oscilloscope equipped with a c.r.t, with several beams. There are a n u m b e r of different types available:

Multi-gun tubes. Figure 9.8(a) shows a c.r.t, with several cathode ray assemblies m o u n t e d in a single tube. Figure 9.8 (b) shows a tube w h e r e each gun or triode assembly has its o w n vertical deflection system but shares c o m m o n horizontal deflection plates. All p h e n o m e n a are displayed with the same sweep speed. 9 Multi-beam tubes. There is a single electron gun for the different deflection systems, typically two. The b e a m is shared b e t w e e n each deflection system by m e a n s of a splitter plate, an

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Figure 9.8 (a) Dual-gun tube. (b) Dual-gun tube with common X-deflection plates (courtesy Enertec Instrumentation Ltd)

How oscilloscopes work (1): the c.r.t.

185

Figure 9.9 Electrode assembly of 'Brimar' mesh p.d.a.c.r.t, type D 1 3 - 5 I GH (courtesy Thorn Brimar Ltd)

a r r a n g e m e n t used in the oscilloscope illustrated as the frontispiece (p. xii). This type of tube is more economical because there is a single gun assembly. However, there is reaction b e t w e e n the two systems, and the brilliance of the displays cannot be adjusted separately. Figure 9.9 shows the construction of the electrode assembly of a m e s h p.d.a, cathode ray tube. The deflection plates are within the cylindrical shield and the mesh covers the square opening at the

Figure 9.I0 'Brimar' spiral p.d.a.c.r.t, type D14-210GH/82 with internal graticule (courtesy Thorn Brimar Ltd)

186

Oscilloscopes

screen current limiter goin-coml~nsat ing cathode driver

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F i g u r e 9.11 The MCP (micr()channel plate) cathode ray tube used in the Tektronix oscillosc()pe type 7104. MCP c.r.t.s are als() used in the model 11302 m a i n f r a m e and in tile 2467. This model for the first time enables an isolated glitch only n a n o s e c o n d s wide to be seen on a portable oscilk)scope. All three models m e n t i o n e d are discontinued, btlt highly valued on the s e c o n d - u s e r m a r k e t (courtesy Tektronix UK Ltd)

How oscilloscopes w o r k (1): the c.r.t.

187

end. The wires of which the mesh is w o v e n are so fine that it is invisible; this also ensures that it is transparent to the beam of electrons. Figure 9.10 shows a high-performance oscilloscope c.r.t, with side connectors to the deflection plates for m i n i m u m capacitance, spiral p.d.a., internal graticule, bonded implosion guard and light guide for graticule illumination. All the measures to maximize the bandwidth of a c.r.t. mentioned p r e v i o u s l y - p.d.a., delay-line deflection plates, scan expansion lenses - were put together in the cathode ray tube used in the Tektronix type 7104 oscilloscope. This instrument boasted a 1 GHz real-time bandwidth, this limit being set by the Y amplifier rather than the c.r.t, itself. The latter could display signals up to 2.5 GHz, were it possible to design suitable wideband drive circuitry. Also, notwithstanding the conflict, explained earlier, between tube design parameters for optimum bandwidth and m a x i m u m writing speed, this tube achieves the remarkable writing speed of 20000cm/lxs, using ASA 3000 film without fogging. (In fact, single shot events at that speed can also be seen comfortably with the naked eye.) The secret is revealed in Figure 9.11, which shows that in addition to the measures already mentioned, the c.r.t, incorporates a microchannel electron multiplier plate. This consists of thousands of short, parallel tubes, each coated internally with a high-resistance film. Each individual tube acts as an electron multiplier by virtue of secondary emission, resulting in 10000 electrons hitting the phosphor for each electron in the beam. Owing to the small spacing between the microchannel plate output side and the aluminized phosphor, together with the high potential difference between them, there is negligible spreading of the output of each microchannel tube, maintaining a small, sharp, spot size.

10

How oscilloscopes work (2): circuitry Figure 10.1 shows the block diagram of a typical dual trace, highperformance oscilloscope. Two identical input channels A and B are switched alternately to a c o m m o n amplifier, which drives a delay line. This is s h o w n diagrammatically as composed of discrete inductors and capacitors, although in a m o d e r n instrum e n t it would usually consist of a length of delay cable. This is similar to coaxial cable, except that it has a centre conductor w o u n d in the form of a spiral and hence provides m u c h greater delay per unit length. As the drive to the trigger circuit is picked off before the delay line, the delay introduced by the latter permits the whole of the leading edge from which the scan was Y

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Figure 10.1 Block diagram of dual trace, mains-operated oscilloscope (courtesy Enertec Instrumentation Ltd)

How oscilloscopes work (2): circuitry

189

triggered to be observed. This assumes of course that the risetime of the leading edge and the 'wake-up time' of the trigger circuit are together less than the delay introduced by the delay line, which is generally tens of nanoseconds. The final Y amplifier produces the p u s h - p u l l voltages that drive the Y plates, and in a higher-performance instrument the peak-to-peak output swings required might be little more than a few tens of volts or less, especially if using a tube with a high p.d.a, ratio and a scan-expansion lens. The X amplifier has to provide several times as m u c h voltage swing as the Y amplifier, as the X-plate sensitivity is less than that of the Y plates. Fortunately, a substantially smaller bandwidth suffices for the X amplifier, easing the circuit design problems: the c.r.t, designer takes advantage of this to maximize the Y-plate sensitivity at the expense of the X-plate sensitivity. The X deflection amplifier is driven with a sawtooth waveform produced by a 'sweep' or 'timebase' generator, which itself is triggered by a pulse from the trigger circuit. The trigger circuit produces a pulse each time the Y input voltage crosses a given threshold voltage, which is usually adjustable by the front-panel trigger level control. Thus the sweep always starts at the same point on the waveform, the sweep generator thereafter being insensitive to further trigger pulses until it has completed both the trace and the following (blanked) 'retrace' or 'flyback'. Circuit elements Traditionally, oscilloscope designers made use mainly of discrete components, especially in critical stages such as the Y amplifier output stage driving the c.r.t, deflector plates. However, integrated circuits are being used to an increasing degree, especially in highperformance oscilloscopes, and this trend will doubtless continue and accelerate. Few if any integrated circuits are produced by the major semiconductor manufacturers specifically for oscilloscopes in the way that i.c.s are mass produced specially for TV sets. The largest oscilloscope manufacturers have their own in-house i.c. facilities, often producing i.c.s in hybrid form, since in scope applications one is always seeking to wring the last ounce of performance out of every circuit. The same consideration is likely

190

Oscilloscopes

to ensure that certain sections of oscilloscopes will continue to be designed using mainly discrete components. Figure 10.2 shows two of the basic circuit 'building blocks' used in oscilloscopes. The long-tailed pair is widely used in both forms shown, the second being especially common in analogue integrated circuits. It provides balanced p u s h - p u l l outputs, even if only one input terminal is driven; i.e. it converts from unbalanced

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How oscilloscopes work (2): circuitry I91 to balanced signals. This is an important function, as oscilloscope inputs are usually 'single-ended' or unbalanced, whereas a p u s h pull or balanced drive is almost invariably applied to the Y (and X) plates. The reason for this is simple. If balanced drive is used, only half the peak-to-peak voltage swing is required at each plate compared to the swing required for the case where only one plate is driven, the other remaining at a constant potential. Thus with balanced drive the supply voltage to the transistors driving the plates can be halved. With only half the voltage across each transistor, the current t h r o u g h it can be doubled w i t h o u t increasing its heat dissipation, which is important in the output stage of a deflection amplifier, as these transistors are invariably run very near the m a x i m u m permitted dissipation. With half the supply voltage and twice the current, the load resistor R E will only be one-quarter of w h a t it would have been for single-ended deflection, resulting in a fourfold increase in bandwidth. The cascode c i r c u i t - Figure 10.2(b) - c a n be seen to consist of a c o m m o n - e m i t t e r stage with a c o m m o n - b a s e stage as its collector load. This a r r a n g e m e n t has two advantages. First, the m a x i m u m voltage that can be applied to TR2's collector is equal to the collector-base b r e a k d o w n voltage Vcb, which for highfrequency transistors is often substantially higher t h a n the c o m m o n - e m i t t e r b r e a k d o w n voltage Vce, enabling a larger output voltage swing to be obtained from the stage. Second, there is inevitably, owing to the construction of a transistor, a capacitance of a few picofarads b e t w e e n its collector and base terminals, denoted Ccb. In the cascode circuit, the input capacitance at the base of TR1 is approximately Ccb ~ + Cbe ~ (where Cbe~ is the base-emitter capacitance of TR1), since the input impedance at the emitter of grounded-base stage TR2 is very low and there is therefore negligible signal voltage at TR1 collector. If a simple c o m m o n - e m i t t e r stage were used in place of the cascode stage, the input capacitance would appear m u c h larger, as the end of Ccb connected to the output would be changing in the opposite sense to the input voltage, by an a m o u n t greater t h a n the input voltage swing. In fact, if the stage gain is A, the input capacitance w o u l d be approximately Cbe + (A + 1 )Ccb, the wellk n o w n Miller effect. If A is large it would prove difficult to drive

192

Oscilloscopes

the stage satisfactorily, a problem that is avoided by the cascode circuit.

Y deflection amplifier Oscilloscope designers frequently make use of the advantages of both the long-tailed pair and the cascode, as shown in Figure 10.3. Here, the total output capacitance Ct shunting R E is equal to Ccb2 p l u s the load capacitance, several picofarads if this is a deflection plate of a cathode ray tube. If both transistors have high cut-off frequencies, t h e - 3 d B bandwidth (70.7 per cent response) of the stage is given b y f _ 3 d B -- 1/2~RLCt, showing that for m a x i m u m bandwidth both RL and Ct should be as small as possible. There is little the oscilloscope designer can do about the plate capacitance of the c.r.t., other than find another tube with the same sensitivity and lower plate capacitance if possible, but

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How oscilloscopes work (2): circuitry I93 TR2 should have both a high collector dissipation rating and a low Ccb. Note that if TR2 is changed for a n o t h e r type w i t h twice the dissipation rating, enabling the standing current to be doubled and R E halved, the b a n d w i d t h would be increased even t h o u g h the Ccb of the m o r e powerful transistor were twice that of the original one. This is because Ccb2 generally constitutes less t h a n 50 per cent of Ct, w h i c h will therefore have increased by a m u c h smaller factor t h a n two.

Inductive peaking A b a n d w i d t h greater t h a n the above f-3 dB can be obtained by the use of inductive peaking circuits to offset the effect of Ct. Note that Ct includes the collector capacitor of the plate-driving transistor, the capacitance of the connecting lead to the plate, and the effective plate capacitance. The last is generally listed by the c.r.t, m a n u f a c t u r e r as Cyl_all, m e a n i n g the capacitance of one Y plate to everything else except the other Y plate, and Cyl_y2 m e a n i n g the capacitance b e t w e e n the Y plates. The effective plate capacitance is Cpe = Cyl-aU + Cy~_y2 if only one plate is driven, or Cpe = Cy~_an + 2Cy~_y2 if, as is usually the case, the two Y plates are driven in antiphase. Figure 10.4(a) shows a deflection-amplifier o u t p u t stage using s h u n t peaking. If we define Q such that Q = L/RLXCt, t h e n if L is chosen such that Q = 0.25 the pulse response of the stage will show no overshoot, while for Q = 0.414 there will be 3.1 per cent overshoot. However, the risetime will be 71 per cent and 59 per cent respectively of that of the same stage w i t h o u t the inductive peaking. By using a capacitance C = 0.22Ct in parallel w i t h a value of peaking inductance L = 0.35RL2Ct, the risetime falls to 56.5 per cent of the u n c o m p e n s a t e d value and the overshoot is only 1 per cent. The above are examples of ' t w o - t e r m i n a l ' c o m p e n s a t i o n networks; i m p r o v e d performance at the expense of increased complexity can be obtained by splitting Ct into its c o m p o n e n t parts. Ccb and Cpe are c o m p e n s a t e d separately; the capacitance of the plate connection lead can be included w i t h either of these two to help m a k e up the relative values of capacitance s h o w n in

194 Oscilloscopes

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How oscilloscopes work (2): circuitry 195

Emitter compensation With the inductive peaking schemes described above, the i m p r o v e m e n t in risetime over an u n c o m p e n s a t e d amplifier is i n d e p e n d e n t of the amplitude of the displayed trace, and is limited to a factor of about 2.5:1 using a four-terminal compensation network. The trend recently has been to a b a n d o n inductive peaking of deflection-amplifier output stages in favour of emitter compensation. This scheme is exemplified in Figure 10.5, which shows the circuit of a Y amplifier designed by the author for m i n i m u m risetime w h e n using a 3BP1, an insensitive and very o u t m o d e d design of c.r.t., but cheap and readily available. Here, the gain of the output amplifier output stage at d.c. and over most of its frequency range is determined by R326, but at higher frequencies C309, 310 tend to bypass R326, resulting in a gain that rises with frequency, compensating for the loading effect of Ct. In fact, the gain of the amplifier transistors is also beginning to fall, with the result that it is not a simple RC load circuit that we are trying to compensate. Consequently, additional c o m p o n e n t s R325, C311 and R308, C314 are included to ensure the s m o o t h roll-off of the frequency response necessary for the faithful reproduction of pulse waveforms. This type of circuit makes use of the fact that a deflection amplifier is always designed to be able to overscan the available screen display area by up to 100 per cent or more, so that the spot can be deflected way b e y o n d the top or b o t t o m of the graticule. W h e n a very fast rising edge is applied to the Y amplifier, the long-tailed pair TR305, 306 will be overdriven, as their emitters are tied together by C309, 3 I0. The result is that all the available tail current (set by R333; TR307, 308 serve only to introduce the Y shift voltage) is m o m e n t a r i l y diverted through, say, TR305 while TR306 is cut off. The load capacitance Ct at each collector is therefore charged at the m a x i m u m possible rate set by the available tail current. As Ct charges, so do the emitter-compensation capacitors C309 and C310, resulting in the steady-state deflection being reached with minimal overshoot. This deflection amplifier is said to be 'slew-rate limited' (Figure 10.6), as the m a x i m u m speed at which the Y-plate voltage can

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How oscilloscopes work (2): circuitry 197 ,/

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change is d e t e r m i n e d by Ct and the m a g n i t u d e of the tail current. Thus, in contrast to inductive peaking, with emitter compensation fast squarewaves are reproduced m o r e faithfully w h e n they are displayed at small amplitude t h a n w h e n displayed at full screen height. Likewise, the - 3 dB b a n d w i d t h is greater for small deflections t h a n large; this explains the growing practice of quoting b a n d w i d t h s at half-screen deflection, w h i c h might possibly be reasonable in the case of dual-trace instruments, but is really not fair in a single-channel scope. As m e n t i o n e d earlier, the Y deflection stage of an oscilloscope is r u n at the highest possible standing current, limited by considerations of device dissipation, in order to achieve the widest possible bandwidth. This has an u n f o r t u n a t e side-effect in an unsophisticated circuit such as that s h o w n in Figure 10.5. Imagine that an a.c. w a v e f o r m with a standing positive d.c. level is to be displayed, and that therefore the trace has been set at the b o t t o m of the graticule in readiness. Consequently, TR305 and 303 are conducting m u c h more heavily t h a n TR306 and 304. Therefore (assuming t h e r m a l equilibrium has been reached) the base-emitter voltage (Vbe) of each of the former pair of transistors will be less t h a n that of the latter pair, since they will be hotter and Vbe has a t e m p e r a t u r e coefficient of a r o u n d - 2 mV/~ Now, w h e n the signal is applied, the trace will be nearer the top of the graticule, so that the dissipation in TR306 and 304 will exceed that in TR305 and 303. Over the next few seconds as the latter two transistors cool and the former heat up, the base-emitter voltages will change accordingly. This will give rise to a spurious

198 Oscilloscopes slow drift of the vertical position of the waveform, due solely to these t h e r m a l effects, and totally unrelated to the input signal. In a professional oscilloscope, great care is taken at the design stage to develop a circuit which does not exhibit these 'thermal tails', by m e a n s of various compensation arrangements. Traditionally, these were exceedingly time c o m s u m i n g to set up and therefore contributed undesirably to the instrument's selling price. W h e n an oscilloscope m a n u f a c t u r e r has an in-house analogue i.c. design and m a n u f a c t u r e facility it is possible to design bespoke circuits which have greater precision and at the same time require fewer setting-up adjustments in production. A good example of such a circuit is the patented 'cascomp', a balanced cascode circuit which is self-compensating for gain errors and, with careful choice of operating points of the transistors, for thermals also, see Figure 10.7. This circuit a r r a n g e m e n t was first used in the 2465 oscilloscope featured in Chapter 3 of the third edition of this book. However, this second generation of advanced Y deflection amplifier does have some

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How oscilloscopes work (2): circuitry 199 I c~176 d | device v j collector

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limitations w h i c h prevent it being suitable for high gain stages. Pressure on space prevents a detailed discussion of these and the circuit's other advantages and disadvantages: for further information see the reference at the end of this chapter. An improved bipolar high-speed analogue i.c., type M377, is used in Tektronix 11000 series oscilloscopes. Each side of the balanced amplifier consists of a long-tailed pair w h e r e the second transistor, Q2 in Figure 10.8, is provided with 100 per cent NFB (negative feedback) from its collector to its base, via Q3- In the practical realization of the circuit, several further developments are incorporated. First, Q3 is made a Darlington c o m p o u n d transistor, for greater transconductance. Second, since the o u t p u t of the stage is taken from the collector of the Darlingtonconnected transistor, the stage gain can be changed by altering its standing current. These additions are s h o w n in Figure 10.9, which represents a simplified version of one of the two gain stages in the M377. This device, w h i c h contains over 700 transistors, also includes a level shift, a variable gain control based on the Gilbert cell and a choice of two bandwidth-limiting filters or the full b a n d w i d t h path. Additional amplifier components, not shown, are included to provide recovery from overdrive to w i t h i n 0.4 per cent in 6 ns. In addition to the variable gain facility, the M377 also implements gain switching over a 50:1 range in a x l , x2, x5 sequence. This simplifies the input attenuators of an

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How oscilloscopes work (2): circuitry 201 description of the Y deflection system by looking at the input attenuator. Traditionally, the Y amplifier of an oscilloscope n o r m a l l y runs at a fixed value of gain, equal to w h a t it provides on the most sensitive range, the exception being i n s t r u m e n t s using the type of special IC described above. For the less sensitive ranges, the input signal is a t t e n u a t e d to bring it d o w n to the same level as on the most sensitive range. Normally, w i d e b a n d u n b a l a n c e d variable attentuators are designed with a low, purely resistive characteristic impedance. However, as previously stated, for oscilloscope w o r k a high input impedance (especially at low frequencies) is generally required, the standard value being 1 MfL At this i m p e d a n c e level the stray capacitance associated with the a t t e n u a t o r resistors, switch, etc. m u s t be taken into account if the a t t e n u a t i o n is to r e m a i n constant over a b a n d w i d t h of even a few megahertz, let alone h u n d r e d s of megahertz. This is achieved by absorbing the stray capacitance of the c o m p o n e n t s into larger, deliberately introduced capacitances and t h e n adjusting the latter so that the frequency response is constant. Figure 10.10 shows a typical input a t t e n u a t o r such as might be found in an oscilloscope of 5 to 10 MHz b a n d w i d t h . It is in fact that used in the Scopex 4S6 oscilloscope. It can be seen that each a t t e n u a t o r pad, e.g. +10 the position using R3 (900 kf~) and R4 (effectively 100 k ~ owing to R9 plus R10 in parallel w i t h it), has a capacitive divider CV4 and C 3 in parallel. CV4 is adjusted so that its value is o n e - n i n t h of C3 + CV9 + the input capacitance of the Y amplifier. Thus the resistive and capacitive division ratios are the same and the a t t e n u a t i o n is i n d e p e n d e n t of frequency. CV9 is used to set the input capacitance of the scope on the most sensitive range to a standard value, while CV1, CV3, CV5 and CV7 enable this same input capacitance to be achieved on all the other input ranges. This is i m p o r t a n t w h e n using a passive divider probe, as described in Chapter 4. R9, C6 a n d CVl0 protect the field-effect transistor forming the first stage of the Y amplifier from damage in the event of a large input at d.c. or low frequency being applied to the oscilloscope w h e n on the most sensitive range, while passing high frequencies largely u n a t t e n u a t e d . It is therefore i m p o r t a n t that large-amplitude signals at high frequencies, e.g. the o u t p u t of

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204

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206

Uscjlloscopes

above signals are disconnected and the single-sided inpiit from the EXT TRIG input socket SKC is selected. When the a.c. coupling switch, S504, is out, the trigger signals are directly coupled-through, but when this switch is in, a.c. coupling is introduced via C 6 0 3 and C 6 0 4 (C601 on external). TR601 and TR602 form a differential buffer amplifier with the d.c. balance controlled by the trigger level control, R602. The differential output from this stage is applied to the comparator, IC602, which has positive feedback applied by R623 to form a Schmitt trigger circuit. The changeover switch, S506, reverses the output frvrii TR601 a n d TR602 to determine tht. trigger slupe. When hot.11S 5 0 4 and S 5 0 5 are 'in' (a.c. and d.c. in forTV ruode), the junction of R603 and CGlO is connected t o ~ l i -c1 1 V supply. T)601 and D 6 0 8 a r e t~roughlirilo cx)ridiiction, while D602 a r i d D604 are rcvcrsc biased. This diverts t h e output o f thc Trigger amplifier away frorn IC602 into TR605, which amplilies the posilive lips of llic waveform orily. TK605 is prevented from saturation by feeding back the peak detected sync pulses via TR607 and TR606 to thc emitter of TR605. These pulscs are amplified hy I C 6 0 l b and applied via R617 and D603 t o the Schinitt trigger. 1C602. 1C601a is used in conjunction with S504 and S505 to disable the sync separator when a.c. o r d.c. is selected. At the fast timchase sweep speeds, S262a is open and TR603 i s cut oft. However, a1 speeds of 100 p d c m and slower, R608 is connected t o + I I V and TR603 i s switched on. This effectively grounds C609 t o inlroducc a n RC integrating time constant into Ihe sync pulse signal path in t h c TV modc to separate out the fra m c' t r igger. The squarewave Iriggc'r output from IC602 is applied (with d.c. bias of zener diode, D 6 0 5 ) as thc clock t o the D-type TTL flip-flop, IC501 a. A positivc.-going triggcr chdgchwill clock thc kistahlc, driving Cj Iow. 111 ttic waiting state, Cj was IiigIi (+4.5v), turning o n TI7261 via R507 a r i d R 2 h 2 , holding Ihe iriput (arid hence Ihc o i i t p i i t ) of thc. operational amplifier, IC261, at 0 V. This timchase ;IrnpliIier is cunnectcd as a direct voltage follower. When the tr-igger signal sends 6 of 1C50 1 a low, the timebase clamp transistor, TR26 1 , is turned o f f . Part of the constant current generated by TR264 flows through the resistor network, R272, to

How oscilloscopes work (2): circuitry 207 charge C263 at a constant rate. The resultant positive-going linear ramp voltage generated at the input of IC261 is buffered by the amplifier to generate the l o w - i m p e d a n c e ramp output. The timebase range switch, $262, selects the tap point on the network, R272, to vary the ramp slope in the 1, 2, 5 sequence over a range of three decades. On all fast sweep ranges TR262 is biased off, but on ramps 0 . 5 m s / c m and slower $262c connects R263 to + l l V . TR262 is t u r n e d on and C264 is effectively connected in parallel with C263 to slow the sweep rate 1000 times. The constant current in the ramp generator is derived from the current mirror circuit formed by TR263 and TR264. The variable gain control, R269, provides an approximate 3:1 range of variation in this current; R506 provides a preset calibration control on the slow sweep rates, only w h e n S262 is closed. W h e n the ramp reaches its m a x i m u m level, the negative bias introduced by R521 and R519 is overcome and TR503 turns on, driving the reset input of the timebase bistable low. As the bistable switches, Q returns high, and TR261 conducts to discharge the timing capacitor(s) and the sweep is complete. However, a hold-off action takes place to inhibit trigger signals during the sweep; this remains for a short period after a sweep to ensure that the ramp potential is fully reset before the next sweep can be triggered. As the ramp goes positive, D506 conducts to charge C502, reverse biasing D503 and turning on TR502. At the end of the sweep w h e n the timebase is reset, Q goes low and the D input follows via the action of D508 and R511. The ramp o u t p u t returns rapidly towards 0 V, but TR502 remains in conduction for a period d e t e r m i n e d by C502 and R518. Only w h e n TR502 turns off can R516 and D507 take the D input high for the bistable to respond to the next clock input. TR501 acts in a w a y similar to TR262 (described above) to introduce additional hold-off time t h r o u g h C501 on the slower half of the timebase ranges. The brightline facility causes the timebase to free-run in the absence of trigger signals. The squarewave o u t p u t from the Schmitt trigger, IC602, is coupled via C615 into the peak detector

diodes, D 6 0 6 and M07, to gcncratc a positive-going signal into thc iicgativc input of ICGOlc, driving its o i i t p u t negative. I n the absence (.)F such Wigger signals for a period dctcrmincd by C618 with R 6 2 7 and R626, the output of I C 60l c goes positive. When TK502 turns oll a t the elid of the hold-off period, D509 conducts to turn on TR504, driving the set output low t o initiate another sweep. This free-run condition is rcmovcd as soon as IC60lc detects a n output from the Schmitt trigger. It can be inhibited also with t h e positive bias via R 6 2 5 if the BRIGHTLINE OFF switch S501 is operated. The X output amplifier is formed by the shunt feedback stage of TR509/TR5 11 driving single-sided into the amplifier stage, TR513 and TR514. The collector output of this stage drives the X deflection plates o f the c.r.t. The gain introduced by TR509/ TR511 is defined in the x5 magnification mode by t.he input resistance, R539, and the feedback resistance, R552. wirh the preset, R553. I n this mode the transistor switch, TR512, is biased o f f . However, in nririiial x l magnification mode, S 507 is open and the c i i r r e n ~in R 5 4 8 turns o n TR51 2, introducing K544 with preset R 5 5 1 as additional feedback to rcducc thr gain of the a i n pl i f ic' r accord i ng l y. The X s h i f t control, R501, introduces a n additional bias input via R541 into the input of the shunt Ieedback arnplifier.

Power supply and c.r.t. circuitry Figure 10.12 is the circuit diagram of the c.r.t. power supplies section of a straightforward oscilloscope, the Scopex 4% mentioned earlier. All the supplies are derived from a mains transformer with a n untapped primary, providing operation from 2 1 0 to 2 5 0 V a.c., 48-60Hz. The 6.3 V secondary winding that supplies the c.r.I. heater is insulated to withstand the full -1.4kV e.h.t. voltage applied t o the c.r.t. cathode/grid circuit. All the d.c. supplies are derived from a single-tapped secondary winding; as is usiially {he case in incxpcnsivc scopcs, thcy arc n o t stabilized. This will cause the deflection sensitivity of i h c c.r.t. to vary wi.th triairis v o l ~ a g c ,bill the design ot the Y amplifier is such that its gain varies with niains voltage i n the inverse se~ise,rnainlaiIiirig thc ovcrall gain scnsitdy coiist~7nta t thc calihraicrl valiir.

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210

Oscilloscopes

Figure 10.13 The self-limiting effect of the microchannel plate used in the now discontinued 2465B compressed the brightness range - see Figure 9.11. Left: a pulse train on the fastest writing-speed scope with a conventional c.r.t, does not reveal the low-level glitch occurring every ten-thousandth pulse. Right: the same pulse train viewed directly on an oscilloscope using a microchannel-plate type c.r.t. Only the most expensive digital storage oscilloscopes can match this performance (courtesy Tektronix UK Ltd)

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Figure 10.14 W i t h a s t o r a g e w r i t i n g s p e e d ( s c c C h a p t e r l l ) o f S n s / d i v , theLA354 is lhc [astest Analogue Storage Oscilloscope available. This remarkable performante is achieved by using a scan converter tube ill conjunction with a TFT-LCD colour screen, i.e. it is an indirect-view oscilloscope (courtesy LeCroy Ltd)

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is 1 he photometric cqu iva Icn t of b ri gh mess. 11 is based on measurcmcnts made with a wnsor having a spectral sensitivity curve rurrecied lo that of the average huimri cyc. The S1 (inlernalional metric standard) units for lrirninance a r e candelas per squarc mctrc, bur. footlamberts arc still used extensively in thy US; 1 footlambert = 0.2919 candelaim’. The term luminance implies that data has been measured o r corrected to incorporate the CIE standard eye response curve for the h u m an eye. CIE is a n abbreviation for Commission Internationale de L‘Eclairage (Internal Commission o n Illumination). The luminance graphs and tables are therefore useful only when the phosphor is being viewed. Phosphor protection When a phosphor is excited by an electron beam with an excessively high current density, a perrnancnl loss of phosphor efficiency m a y occur. The light output of the damagcd phosphor will be reduced, and in cxircmc cases cornplere desrruction of thc phosphor may rcsulr. Darkening o r burning occurs whcn the

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Comments Replaced by GH (P3 l) in m o s t applications Television displays Long decay, d o u b l e - l a y e r screen For p h o t o g r a p h i c applications G e n e r a l purposes, brightest available phosphor L o w refresh rate displays High c u r r e n t density phosphor Bistable storage M o n o c h r o m e TV displays

i Tektronix is adopting the Worldwide Phosphor Type Designation System (WTDS) as a replacement for the older JEDEC 'P' number system reference. The chart lists the comparable WTDS designations for the most common 'P' numbers. 2 Measured with Tektronix J16 Photometer and J6523 Luminance Probe which incorporates a CIE standard eye filter. Representative of 10 kV aluminized screens. GH (P31) as reference. 3 BE (P11) as reference with Polaroid 612 or 106 film. Representative of 10kV aluminized screens. 4 Not available. 5 Yellowish-green phosphorescence. BE (P11) phosphor has a different spectral output from GH (P31) phosphor standard and more closely matches the sensitivity spectrum of silver halide film types. While photographic writing speed is approximately two times the GH (P31) rate, the visual output luminance is approximately 15% of GH (P31) phosphor standard, using Polaroid Film Type 107, 3000 ASAw/out film fogging.

252 Oscilloscopes heat developed by electron b o m b a r d m e n t cannot be dissipated rapidly e n o u g h by the phosphor. The two most important and controllable factors affecting the occurrence of burning are b e a m - c u r r e n t density (controllable with the intensity, focus and astigmatism controls) and the length of time the beam excites a given section of the phosphor (controllable with the time/div control). Of the total energy from the beam, 90 per cent is converted to heat and 10 per cent to light. A phosphor must radiate the light and dissipate the heat, or like any other substance it will burn. Remember, burning is a function of intensity and time. Keeping the intensity down or the time short will save the screen.

Photographic writing rate Photographic writing rate is a measure of the scope/camera/film's capability to record high-speed signals. Recording high-speed signals on film is dependent on at least three factors: the oscilloscope used, film characteristics, and the camera. For m a x i m u m writing rate capability, the objective is to get as m u c h light energy to the film surface as possible. Since each c o m p o n e n t affects photographic writing rate, the selection for top performance is important. The phosphor offering the highest photographic writing rate is BE (P11). A c.r.t, with this p h o s p h o r is therefore usually specified for an oscilloscope which is required to record photographically very fast single events, which leave too faint a trace to be observed visually. However, a microchannel plate c.r.t. (Figure 9.11) enables one to see clearly single shot events at the full bandwidth of the oscilloscope. For this reason, GH (P31) p h o s p h o r is standard on MCP c.r.t.s. Note The information in this appendix is reproduced by courtesy of Tektronix UK Ltd.

Appendix 2

Oscilloscope manufacturers and agents The following list gives the names, addresses and sales office telephone/fax n u m b e r s of most of the manufacturers of oscilloscopes and PC-oscilloscope adapters whose products are readily available. The information is believed to be correct at the date of publication but no responsibility can be taken for errors or omissions. For overseas manufacturers, the address of the parent c o m p a n y is given, as also is the address of the UK subsidiary, UK sales office or agent as appropriate, w h e r e k n o w n . W h e r e an agent is given, this is not necessarily the distributor or main agent. Manufacturers of some related instruments (e.g. panoramic receivers, spectrum- and network-analysers, logic analysers, recorder/oscilloscopes) are also listed. Tel: = telephone Fax: = facsimile Agilent Technologies UK Limited (formerly Hewlett-Packard), Cain Road, Bracknell, Berks RG12 1HN UK. Tel: 01344 366666. Fax: 01344 362852. Agilent Technologies Inc., 9780 S. Meridian Boulevard, Englewood, CO. 80112. Tel. 00 1 800 8 2 9 4 4 4 4 . A m p l i c o n Liveline Ltd, Centenary Industrial Estate, Hollingdean Road, Brighton, East Sussex BN2 4AW UK. Tel: 01273 570220. Fax: 01273 570215. Manufacturer of PC plug-in DSO modules. Anritsu Corporation, 5 - 1 0 - 2 7 Minamiazabu, Minato-ku, Tokyo Fax: 106-8570, Japan. Tel: 81- 3- 3446-1111. 8 1 - 3 - 3 4 4 2 - 0 2 3 5 . Manufacturer of spectrum and n e t w o r k analysers. Anritsu Ltd, Capability Green, Luton, Beds. LU1 3LU, UK. Tel: + 4 4 - 1 5 8 2 - 4 1 8 8 5 3 . Fax: + 4 4 - 1 5 8 2 - 3 1 3 0 3 . A S M A u t o m a t i o n Sensors M e a s u r e m e n t Ltd, Imperial House, St Nicholas Circle, Leicester LE1 4LF UK. Agent for Hioki.

254 Oscilloscopes A s t r o - M e d , Inc., Astro-Med House, 11 Whittle Parkway, Slough SL1 6DQ, UK. Tel: 01628 668836. Fax: 01628 664994. Astro-Med, Inc., Astro-Med Industrial Park, West Warwick, Rhode Island, 02893 USA. Tel: (401 ) 828-4000. Fax: (401 ) 822-2430. Cell SA., 12 avenue des PrOs, F-78059 St-Quentin-Yv. Cedex France. Tel: 33 (0) 144 O1 22. Fax: 33 (0) 144 01 33. M a n u facturer of PC DSO modules. C h a u v i n A r n o u x UK Ltd, Waldeck House, Waldeck Road, Maidenhead SL6 8BR. Tel: 01628 788888. Fax: 01628 628099. F e e d b a c k I n s t r u m e n t s Ltd, Test and M e a s u r e m e n t Division, Park Road, Crowborough, Sussex TN6 2QR UK. Tel: 01892 653322. Fax: 01892 663719. Agent for Hameg, Hitachi, ITT Metrix, K e n w o o d and Tektronix. Fluke (UK) Ltd, Colonial Way, Watford, Herts WD2 4TT UK. Tel: 01923 240511. Fax: 01923 225067. Fluke Corporation, PO Box 9090, Everett, WA 98206 USA. Tel: 00 1 800 4 4 3 - 5 8 5 3 . Fax: 00 1 425 356-5116. Fluke E u r o p e BV, PO Box 1186, 5602 BD Eindhoven, The Netherlands. Tel: 00 31 (0)40 2 678 200 Fax: 00 31 (0)40 2 678 222. Gould Nicolet Technologies, Roebuck Road, Hainault, Essex IG6 3UE UK. Tel: 0208 500 1000. Fax: 0208 501 2438. Gould I n s t r u m e n t Systems Inc., 8333 Rockside Road, Valley View, OH 44125-6100. Tel: (216) 328 7000. Fax: (216) 328 7400. Offices in France, Germany, Italy, China etc. Hameg GmbH, Kelsterbacher Str. 15-19 6000 Frankfurt am Main 71, Germany. Tel: (069) 6 7 8 0 5 - 0 . Fax: (069) 6780513. Hameg Ltd, 7 4 - 7 8 Collingdon St, Luton, Beds LU1 1RX UK. Tel: 01582 413174. Fax: 01582 456416. H e w l e t t - P a c k a r d - see Agilent Technologies. Hioki E.E. Corporation, Koizumi, Ueda, Nagano, 386-1192, Japan. Tel: +81-268-28-0562. Fax: +81-268-28-0568. Hitachi D e n s h i (UK) Ltd, 14 Garrick Industrial Centre, Irving Way, Hendon NW9 6AQ UK. Tel: 0181 202 4311. Fax: 0181 202 2451. See also Thurlby-Thandar Ltd. I w a t s u Electronics Corporation, 1-7-4 Kugayama, SuginamiKu, Tokyo 168-8501, Japan. Tel: 0081 35370 5111. Fax: 0081 35370 5119.

Oscilloscope manufacturers and agents 255 K e n w o o d TMI Corporation, 1-16-2, Hakusan, Midori-Ku, Yokoh a m a City 226-8525, Japan. K e n w o o d UK Ltd, Kenwood House, Dwight Road, Watford, Herts WD1 8EB UK. Tel: 01923 816444. Fax: 01923 819131. K i k u s u i Electronics Corporation, 1-1-3 Higashi-Yamata, Tsuzuki-Ku, Yokohama 224-0023, Japan. Tel: 0081 4559 30200. Fax: 0081 4559 37591. Leader Electronics Corporation, 2 - 6 - 3 3 Tsunashiria Highashi, Kohoku-ku Yokohama, Japan. Tel: 45 541 2123. Fax: 45 544 1280. See also Thurlby-Thandar. LeCroy Corporation, 700 Chestnut Ridge Road, Chestnut Ridge NY 10977 USA. Tel: (+1) 914 578 6020. Fax: (+1) 914 578 5985. LeCroy Corporation, 27 Blacklands Way, Abingdon Business Park, Abingdon, Oxon OX14 1DY UK. Tel: 01235 533114. Fax: 01235 528796. M a r t r o n - see Yokogawa. M e t r i x - see Chauvin Arnoux. National Panasonic (registered trade mark of Matsushita Comm u n i c a t i o n s - see Panasonic). Nicolet I n s t r u m e n t - see Gould Nicolet. P a n a s o n i c - see Farnell Instruments Ltd. Philips Test & M e a s u r e m e n t - see Fluke. Pico Technology Ltd. 149-151 St Neots Road, Hardwick, Cambridge CB3 7QJ. Tel: +44 (0) 1954 211716. Fax: +44 (0) 1954 211880. Manufacturer of PC DSO modules. Powertek, Unit 148, Beecham Road, Reading RG30 2RE. Agent for CELL. Siemens plc I n s t r u m e n t a t i o n , Sir William Siemens House, Princess Road, Manchester M20 8UR UK. Tel: 061 446 5270. Fax: 061 446 5262. Tektronix, Inc. PO Box 500, Beaverton, Oregon, 97077-0001 USA. Tel: (503) 627 6905. Fax: (503) 627 6611. Offices t h r o u g h o u t the world. Tektronix UK Ltd, The Arena, Downshire Way, Bracknell, Berks RG12 1PU UK. Tel: 01344 392400. Fax: 01344 392403. Telonic I n s t r u m e n t s Ltd, Tootley Industrial Estate, Tootley Road, Wokingham, Berks RG41 1QN UK. Tel: 0118 978 6911. Fax: 0118 979 2338. Agent for Kikusui.

256 Oscilloscopes T h u r l b y - T h a n d a r Ltd, Glebe Road, Huntingdon, Cambs PE18 7DX UK. Tel: 01480 412451. Fax: 01480 450409. Manufacturer of PC DSO modules. Agent for Hitachi, Leader, TrioKenwood. T r i o - K e n w o o d - see Kenwood. Unigraf Oy, Ruukintie 3, Fin-02320, Espoo, Finland. Tel: +358 (0)9 859 550. Fax: +358 (0)9 802 6699. Manufacturer of PC DSO Units. Wavetek Ltd, Hurricane Way, Norwich, Norfolk NR6 6JB UK. Tel: 44 (0)1603 256600. Fax: 44 (0)1603 483670. Manufacturer of oscilloscope calibration equipments. Yokogawa Electric Corporation, T &M Business Division, 155 Takamuro-cho, Kofu-shi, Yamanshi-ken, 400, Japan. Tel: 8 1 - 4 2 2 - 5 2 - 6 6 1 4 . Fax: 81-422-52-6624. Offices in USA and Europe. Yokogawa Martron Ltd, Wellington Road, High Wycombe, Bucks HP12 3PR UK. Tel: 01494 459200. Fax: 01494 535002.

Index

ADC (analogue to digital converter), 115, 132, 141 flash, 128 resolution, 129 SAR (successive approximation), 128 Add s e e Vertical modes Alias, -ing, 104 detect circuit, 136 perceptual, 132, 136 Alternate s e e Vertical mode, Display, Trace Aluminising, 177, 187 Arming, 24, 25, 121 Astigmatism, 20, 177 Attenuator (input), 200 Auto brightline s e e Brightline Averaging, 138 exponential, 140 stable, 141 Axis, 1

Babysitting, I46, 147 Backup, batteries, 20 Balanced, 69, 190 TDR measurements, 161 circuits, 69 measurements, 69 Bandwidth, 18, 73, 82, 140, 193, 197 analogue (of DSO), 128 limit(ing), 22 optical, 169real time, 125

resolution, 164 single shot, 125, 128 video, 160, 164 Battery, -ies: dry, rechargeable, 150 charger, 150 Beam, 176dual, 65 flood, s e e Cathode ray tube BER (bit error rate), 75 Blanking, 97, 179 Blooming (of storage crt trace), 249 Brightline, 16 Brilliance: control, 11 modulation s e e Z modulation Burn(ing), 12

Calibration, 28 scope cal output, 22 calibrators, 45 Cameras (scope), 42-45 Cartesian s e e Coordinates Cascode, 191Cathode-ray tube (c.r.t.), 8, 117, 176 dual beam, 66, 67 electrostatic deflection, 176 magnetic deflection, 176 long persistence, s e e Phosphor microchannel plate, 186 screen, 176single beam, 65

258

Oscilloscopes

Caihodc-ray tubc (c.r.1.) - corzid. storage: 2 1 3 direct view, 2 13mllect.or, 2 17erasing, 221 a u t o erase, 230, 2 4 0 flood gun, 220phosphor target, 22 1 transmission, 240bistable, 242 half-tone, 243save mode, 245 variable persistence, 245 transfer, 246indirect view, 247CCDs (charge coupled devices), 130 Chop see Vcrtical inodes CMRR, 69 Comrnon mode, 22, 6 9 , I62 Compensation, 193 rrrtittrr --, 105 Cornponeni tester, 8 5 Contrast, 225-, 243Coordiriatcs, 1, 2 Coupling, I 3 Crosstalk, 67, 162 Current mirror, 207 Cursor (measurements), 26, 27

Delay: 26 cable, 188 line, 93, 105, 172, 188 pre (post) trigger, see Trigger (ing) Digital storage oscilloscope, 115-148 Disasserriblcrs, 167 r)isconrinuity, see Rcflcction. Dispersion, set’ Span

Display, 132 AltlChop, 29 Hi[-inapped, 76, 117, 143 Falsc, 103 Disturtiori, 80 crossover, 8 I tutal harmonic, 81 Distributed amplifier, 89 Dot joining, see Interpolation, linear Droirivich transmitter, 72 DSO, see Digital storage oscilloscope DSP (digital signal processing), 76 ECI. (emittcr couplcd logic), 50, 148 Electron, 3 , 2 15gun, 177microchannel miiltiplier platc, 1x7 EMC: (electromagnetic coriipatitdity), 158 Erivclopc iiiodc, 143, 145, 147 Eqiiivalcnt timc niodr, 326Expansion: post storage -, 178 Eve diagrams, 73+

Field grid, 181 Filters, 48, 4 9 Flicker, 6, 66 Floodheam, floodgun, see Beam and Cathode ray tube Flyback (blanking), 6, 125, 179, 189 Focus, 12, 20, 177 control, 12, 20, 176 clcctrodc, 177 Fq;iIig, 45

Chapter title 259 Gate: output pulses (A and B), 30 m e m o r y - , 98 Gaussian distribution, 230 Geometry, 178 Gilbert cell, 199 Glitch capture, 124, 146 GPIB (IEEE488) bus, 30 Graph, 1Graticule(s), 4, 12, 16, 20, 46, 187 illumination, 12, 20 special (TV etc.), 49

Hardcopy output, 155 Harmonic(s), 82 hertz, 6

I.C., s e e Integrated circuit. Implosion guard, 187 Input: attenuator, 90 x *-, 12 Integrate mode, 235 Integrated circuits, 189, 198Intensity, 11, 20 Modulation, s e e Modulation Interpolation (linear, pulse, sine), 125, 130, 132, 144 Invert, s e e Vertical modes -

LED light emitting diode, 169 Line (mains), s e e Mains Line (TV sync), s e e Triggering. Linear interpolation, s e e Interpolation. Lissajous figures, 16, 70-72 Liquid crystal display, s e e LCD Logic state analysers, s e e LSAs Long-tailed pair, 190LSAs, 166

MAG-nifier, 23 Mains supply: indicator (light), 11 isolation, 49-51 Memory: acquisition, 124 display, 125 Miller effect, 191 Mismatch, 160 Mode: Alt/Chop, 22, 67, Envelope, s e e envelope Epson Quad Graphics-, 159

Noise, 63, 64, 75, 81, 90, 103, 109, 138-220 signal to noise ratio, 75, 140Nyquist rate, 133, 144

Jitter, 110,

Kickout,

see

Sampling gate

LCD liquid crystal display, 1, 3, 117, I37

Optical time-domain reflectometer, s e e OTR Optoelectronics, 168 Origin, i Oscilloscope (scope): battery operated, 50, 149digital sampling, 171

260

Oscilloscopes

Oscilloscope (scapc) - contd. display, 159 long persistence, 152 rriairifrarrie, 19, 3 1 plug-ins, 18, 31 portable, 18, 32 real-time, 8 recording, I 5 5 sampling, 88- 1 1 4 noise, 9 0 stand-alone, 19 storage: analogue (c.r.t.), 1 3 8 digital (DSO), 1 1 5-148 real time, 117 OTR, 168-

Overshoot, 84, 194

Parallax, 16, 20 Parasilic oscillatirms. It; PC (pci-sonal computrr), 159 PDA, 178, 180, 187 Peaking, coniprnsation, 8 3 , 1 4 3 Persistence: infinite -, 143 PGL Hewletr-Packard Graphics Language. I 5 9 Phase shift (lag, leadj. 6 3 Phosphor(escence), 152, 177 long persistence, 6, 152, 2 14 Post deflection acceleration, SPC PDA Power supply, circuitry, 19 Prediction time, 107 Pre-trigger store (-age), 119Probe(sj, 2 1 active, 38 FET -, 2 12 curi-cnt, 38

differential, 36 passivc, 3 3 - 3 7 , 52-54, 201 PSI< (B-, Q - ) , 73 Pulse interpolation, see Interpolation

Q, 193

RAM (random access memory). 115, 120, 124, 132

dual port, 120 Raster, 117 Ratemeter, 109, 1 1 1 Readout, 20messages/warnings, 26, 49 scale factors, 27, 49 Record length, 137 Recorder: traiisictit -, 174 wavrfot-m -, 158 XY-, Y'I -, 155 Rccurrcnt tnodc, see R d r d i rriodc

Reflection , 160 cocfficicnt, I 0 1 Refresh niode, 122 Reset, 2 4 Resolution, 141 Retrace, 6, 125, 179, 189 Ringing , see Overshoot Risetime, 20, 84, 160, 193 R o l l mode, 1 18 RS232/423 interface, 150, 159

S b H (\ample a n d hold), 129, 1 32 Sdfety certification, 150, 151 Sampling, 88 l,low-l,y, I D I effitirricy, 0 7

Chapter title 261 equivalent time, 117, 126 gate, 95, kickout, 97, 113 interleaved, 128 random, 93, 106 multiple point, 127 sequential, 90, 126 Scan: expansion lens, 181, 187, see also Sweep Screen, 3 Secondary emission, 2 1 5 Self-test, 20 Sequential mode, 126 Servicing, 77 Shift (control), 13, 21 Signal processing, 125, 138 Signal-to-noise ratio, 140 Sine interpolation, see Interpolation Sine wave, 4 Single shot display, 24, 121, 179, 184 Slew-rate, 82, 195 Smoothing, 102, 113, 138 Span, 164 Spectrum analyser, 162 Splitter plate, 65 Staircase generator, waveform, 95, 96, 110 Sweep, 3, 189

Target, 2 1 5 storage - backplate, 223 TDR, 160 optical -, 171 Text, 27, 28 The Open University, 159 Thermal: energy, 216

tails, 198 Timebase, 13, 189, 2 0 3 A (main), 23 B (delaying), 2 5 circuitry, 203 Time domain reflectometer, see TDR Trace, 3, 6 *- finder, 54-56 alternate, 22, 66 chopped, 22, 66 dual, 65 expansion, 69, 137 post storage, 138 find(ing), 5 4 - 5 6 INVert, 22 rotation, 12, 20 separation, 25, 26 Trigger(ing), 4, 13, 23, 2 0 3 a.c., 24 auto, 14, 24, 58 circuitry, 4, 92 countdown, 92 enable, 63 external, 8, 61 glitch, 63 HF reject, 24, 62 hold-off, 25, 62, 93 hysteresis, 63 interval, 65 level, 13, 23, 62 LF reject, 24, 62 manual (normal), 62 mixed, 66, 68 normal, 66 pattern, 65 post-, 121 pre ~-, 106, 121 single shot, 66, 121 slope, 13, 23 TV (line and frame), 79

262

Oscilloscopes

Trigger(ing) - c o n t d . Vertical, see Trigger(ing), mixed window, 63 TTL, 55, 59 TV, 24, 77

VAR (-iable controls), 21, 23, 61 Vertical modes, 21 Viewing hoods, 41 Voltage standing wave ratio, see VSWR VSWR, 161

Waveform: 59 periodic, 7 recorders, 155 repetitive, 57 Writing speed, 12, 65, 183, 187 photographic, 183, 187, 252, 253

X-Y mode, 13, 151

Z modulation, 16, 73, 15i, 179

Oscilloscopes,

Oscilloscopes, Fifth Edition

Digital Storage Oscilloscopes

Oscilloscopes: how to use them, how they work

Oscilloscopes,

Oscilloscopes, Fifth Edition

Digital Storage Oscilloscopes

Oscilloscopes: how to use them, how they work

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